TC412 Microwave Communications. Lecture 8 Rectangular waveguides and cavity resonator

Transcription

1 TC412 Microwave Communications Lecture 8 Rectangular waveguides and cavity resonator 1

2 TM waves in rectangular waveguides Finding E and H components in terms of, WG geometry, and modes. From xye u E ( ) 0, Expanding for -propagating field for the lossless WG gets where E x E y ( ) u E E E ( x, y) e j 2

3 Method of separation of variables (1) Assume E ( x, y) XY where X = f(x) and Y = f(y). Substituting XY gives 2 2 d X d Y 2 2 Y X ( ) u XY dx dy and we can show that for lossless WG. 1 d Y 1 Y dy X 2 2 u d X dx

4 Method of separation of variables (2) Let and then we can write 2 1 x X dx dy y 2 Y dy 2 d X u x y. We obtain two separate ordinary differential equations: 2 d X x X dx 2 dy yy dy 4

5 General solutions X ( x) c cos x c sin x 1 x 2 y y Y ( y) c cos y c sin y 3 4 x Appropriate forms must be chosen to satisfy boundary conditions. 5

6 Properties of wave in rectangular WGs (1) 1. in the x-direction E t at the wall = 0 E (0,y) and E (a,y) = 0 and X(x) must equal ero at x = 0, and x = a. Apply x = 0, we found that C 1 = 0 and X(x) = c 2 sin( x x). Therefore, at x = a, c 2 sin( x a) = 0. a m x ( m 0,1,2,3,...) x m. a 6

7 Properties of wave in rectangular WGs (2) 2. in the y-direction E t at the wall = 0 E (x,0) and E (x,b) = 0 and Y(y) must equal ero at y = 0, and y = b. Apply y = 0, we found that C 3 = 0 and Y(y) = c 4 sin( y y). Therefore, at y = a, c 4 sin( y b) = 0. b n y ( n 0,1,2,3,...) y n. b 7

8 Properties of wave in rectangular WGs (3) m n u a b rad / m and h 2 2 m n a b therefore we can write mx ny j E E0 sin sin e V / m a b 8

9 TM mode of propagation Every combination of integers m and n defines possible mode for TM mn mode. m = number of half-cycle variations of the fields in the x- direction n = number of half-cycle variations of the fields in the y- direction For TM mode, neither m and n can be ero otherwise E and all other components will vanish therefore TM 11 is the lowest cutoff mode. 9

10 TM 11 field lines Side view End view 10

11 Cutoff frequency and wavelength of TM mode f c, mn 2 2 h 1 m n 2 2 a b H c, mn m n a b m 11

12 Ex2 A rectangular wg having the interior dimension a = 2.3cm and b = 1cm filled with a medium characteried by r = 2.25, r = 1 a) Find h, f c, and c for TM 11 mode b) If the operating frequency is 15% higher than the cutoff frequency, find (Z) TM11, () TM11, and ( g ) TM11. Assume the wg to be lossless for propagating modes. 12

13 TE waves in rectangular waveguides (1) E = 0 From H ( ) H xy u Expanding for -propagating field for a lossless WG gets H x H y ( ) (, ) u H x y where H H ( x, y) e j 13

14 TE waves in rectangular waveguides (2) In the x-direction Since E y = 0, then from E y j H j u x u E y we have x H 0 at x = 0 and x = a 14

15 TE waves in rectangular waveguides (3) In the y-direction Since E x = 0, then from E x j H j u y u E x we have y H 0 at y = 0 and y = b 15

16 Method of separation of variables (1) Assume H ( x, y) XY then we have X ( x) c cos x c sin x 1 x 2 y y Y ( y) c cos y c sin y 3 4 x 16

17 Properties of TE wave in x-direction of rectangular WGs (1) 1. in the x-direction at x = 0, at x = a, H 0 x dx ( x) xc1sin xx xc2cos xx 0 dx c 2 0. x H 0 dx ( x) dx c x 1 sin x 0 x 17

18 Properties of TE wave in x-direction of rectangular WGs (2) a m x ( m 0,1,2,3,...) x m. a 18

19 Properties of TE wave in y-direction of rectangular WGs (1) 2. in the y -direction at y = 0, H 0 y dy ( y) yc3sin y y yc4cos y y 0 dy c 4 0 at y = b, y H dy ( y) dy 0 c y 3 sin y 0 y 19

20 Properties of TE wave in y-direction of rectangular WGs (2) b n y ( n 0,1,2,3,...) y n. b For lossless TE rectangular waveguides, mx ny j H H0 cos cos e A/ m a b 20

21 Cutoff frequency and wavelength of TE mode f c, mn 2 2 h 1 m n 2 2 a b H c, mn m n a b m 21

22 TE 10 field lines Side view End view Top view 22

23 A dominant mode for TE waves For TE mode, either m or n can be ero, if a > b, is a smallest eigne value and f c is lowest when m = 1 and n = 0 (dominant mode for a > b) h a ( f ) c TE a up 2a H ( c ) TE 2a m 10 23

24 A dominant mode for TM waves For TM mode, neither m nor n can be ero, if a > b, f c is lowest when m = 1 and n = 1 ( f ) c TM a b H ( ) c TM m a b 24

25 Ex1 a) What is the dominant mode of an axb rectangular WG if a < b and what is its cutoff frequency? b) What are the cutoff frequencies in a square WG (a = b) for TM 11, TE 20, and TE 01 modes? 25

26 Ex2 Which TM and TE modes can propagate in the polyethylene-filled rectangular WG ( r = 2.25, r = 1) if the operating frequency is 19 GH given a = 1.5 cm and b = 0.6 cm? 26

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29 Rectangular cavity resonators (1) At microwave frequencies, circuits with the dimension comparable to the operating wavelength become efficient radiators An enclose cavity is preferred to confine EM field, provide large areas for current flow. These enclosures are called cavity resonators. b There are both TE and TM modes but not unique. a d 29

30 Rectangular cavity resonators (2) -axis is chosen as the reference. mnp subscript is needed to designate a TM or TE standing wave pattern in a cavity resonator. 30

31 Electric field representation in TM mnp modes (1) The presence of the reflection at = d results in a standing wave with sin or co terms. Consider transverse components E y (x,y,), from B.C. E y = 0 at = 0 and = d 1) its dependence must be the sin type 2) p d similar to E x (x,y,). ( p 0,1,2,...) 31

32 32 Electric field representation in TM mnp modes (2) From H vanishes for TM mode, therefore x u u y u u H E j j E y x H E j j E x y 2 2 x y E j E x h E j E y h

33 Electric field representation in TM mnp modes (3) If E x and E y depend on sin then E must vary according to cos, therefore p E( x, y, ) E( x, y)cos V / m d E 0 m x n y p sin sin cos V / m a b d u p m n p fmnp resonant frequency H 2 a b d 33

34 Magnetic field representation in TE mnp modes (1) Apply similar approaches, namely 1) transverse components of E vanish at = 0 and = d - require a sin p factor in E x and E y as well as H. d 2) factor indicates a negative partial derivative with. - require a cos p factor for H x and H d y p H ( x, y, ) H ( x, y)sin A/ m d m x n y p H0 cos cos sin A/ m a b d f mnp is similar to TM mnp. 34

35 Dominant mode The mode with a lowest resonant frequency is called dominant mode. Different modes having the same f mnp are called degenerate modes. 35

36 Resonator excitation (1) For a particular mode, we need to 1) place an inner conductor of the coaxial cable where the electric field is maximum. 2) introduce a small loop at a location where the flux of the desired mode linking the loop is maximum. source frequency = resonant frequency 36

37 Resonator excitation (2) For example, TE 101 mode, only 3 non-ero components are E y, H x, and H. insert a probe in the center region of the top or bottom face where E y is maximum or place a loop to couple H x maximum inside a front or back face. Best location is affected by impedance matching requirements of the microwave circuit of which the resonator is a part. 37

38 Coupling energy method place a hole or iris at the appropriate location field in the waveguide at the hole must have a component that is favorable in exciting the desired mode in the resonator. 38

39 Ex3 Determine the dominant modes and their frequencies in an air-filled rectangular cavity resonator for a) a > b > d b) a > d > b c) a = b = d 39