From 1rst order to Higher order Sliding modes

Size: px
Start display at page:

Download "From 1rst order to Higher order Sliding modes"

Transcription

1 From 1rst order to Higher order Sliding modes W. Perruquetti Ecole Centrale de Lille, Cité Scientifique, BP 48, F Villeneuve d Ascq Cedex - FRANCE. tel : fax : wilfrid.perruquetti@ec-lille.fr November 2010 / Douz

2 Table of Contents 1 Differential Inclusion: Notion of solution 2 3

3 Introduction A simple stabilization problem: double integrator How to stabilize? ẍ = u (1) ẋ 1 = x 2 ẋ 2 = u (2) F1 car.

4 Introduction A simple stabilization problem: double integrator u Classical solution: State feedback State feedback which is to frequency approach or polynomial approach x x Assume that (x 1, x 2 ) is available Time (secs) 1 0 x Time (secs) Stabilization even with a bounded control!! Time (secs) x1 Sate feedback: stabilization of (2) with u = x x 2

5 Introduction A simple stabilization problem: double integrator A variable structure controller If the speed is not available : Observer (dynamic extension) An alternative solution with output feedback? The simplest function being: u = f(x 1 ) (variable α) u = αx 1 ẋ 1 = x 2 ẋ 2 = α x 1 (3)

6 Introduction A simple stabilization problem: double integrator Strategy 1: position x available and the signum of ẋ (in fact of xẋ ) How to play with α? ẍ + αx = 0 x 1 (t) = x 0 cos( αt) + ẋ0 α sin( αt) (4) x 2 (t) = x 0 α sin( αt) + ẋ0 cos( αt) (5) (x 0 αx1 + ẋ0 α x 2 ) 2 + (ẋ 0 x 1 x 0 x 2 ) 2 = (x 2 0 α + ẋ 2 0 α ) 2 (6) Solutions are ellipsoids

7 Introduction A simple stabilization problem: double integrator Area I : x 1 x 2 < 0, α I = 1 Area II : x 1 x 2 > 0, α II = 2 After 2k + 1 switching: l 2k+1 = α I α II l 0

8 Introduction A simple stabilization problem: double integrator Strategy 2: position x and velocity ẋ are available How to play with α? α = 1 ẍ + x = 0 Solutions are ellipsoids Phase portrait

9 Introduction A simple stabilization problem: double integrator α = 1 Phase portrait ẍ x = 0 Solutions are hyperbolas x(t) = x 0 cosh(t) + ẋ 0 sinh(t) One stable and one unstable manifold

10 Introduction A simple stabilization problem: double integrator Area I : α I = 1 4 Commande par mode glissant yzone I : k Z 1.5 x 1 < 0 x 1 + x 2 X 0 X X n WI y 1 or X x 1 > 0 x 1 + x 2 X X m Zone II : k Area II : α II = 1 y X m X X x 1 0 x 1 + x y 2 < X 0n X or X -1.5 WW IW 1 WW 1.5 x 1 0 x 1 + x 2 > 0 W. PERRUQUETTI 14

11 Introduction Some first questions Problems: Notion of solution, Discontinuous Control (damaging the actuators), How to find the switching logic? Panis (Canada 97)

12 Introduction Variable Structure System Differential Inclusion: Notion of solution 4 Commande par mode glissant General Problem formualtion for VSS: Problématiques générales ẋ = f i (t, x, u i ) SS : Find the switching logic and the DX control? F DT I T X U I X2 I ouver les commandes et les iques de commutations!! s 2 2 s s s e e

13 Introduction Sliding Mode Control CMG : SMC (1rst order and Higher): 4 Commande par mode glissant n n i Ewc{cx Slap principle Le principe des «baffes» ve{'f i Ewc{cx W. PERRUQUETTI

14 Introduction Sliding Mode Control Objective To constrain the trajectories of system ẋ = f(x) + g(x)u to reach, in a finite time, and then, to stay onto the sliding surface chosen according to the control objectives Sliding mode control { u u = + (s) if sign(s(x)) > 0 u s) if sign(s(x)) < 0 A simple sliding mode control design with u + u u = u eq + u disc given by s = ṡ = 0, W. (invariance Perruquetti of1rst the to HOSM sliding surface)

15 Introduction Sliding Mode Control Objective To constrain the trajectories of system ẋ = f(x) + g(x)u to reach, in a finite time, and then, to stay onto the sliding surface chosen according to the control objectives Sliding mode control { u u = + (s) if sign(s(x)) > 0 u s) if sign(s(x)) < 0 A simple sliding mode control design with u + u u = u eq + u disc given by s = ṡ = 0, W. (invariance Perruquetti of1rst the to HOSM sliding surface)

16 Introduction Sliding Mode Control Objective To constrain the trajectories of system ẋ = f(x) + g(x)u to reach, in a finite time, and then, to stay onto the sliding surface chosen according to the control objectives Sliding mode control { u u = + (s) if sign(s(x)) > 0 u s) if sign(s(x)) < 0 A simple sliding mode control design with u + u u = u eq + u disc given by s = ṡ = 0, (invariance of the sliding surface) u disc = ksign(s), (convergence in finite time onto the surface)

17 Introduction Sliding Mode Control Objective To constrain the trajectories of system ẋ = f(x) + g(x)u to reach, in a finite time, and then, to stay onto the sliding surface chosen according to the control objectives Sliding mode control { u u = + (s) if sign(s(x)) > 0 u s) if sign(s(x)) < 0 A simple sliding mode control design with u + u u = u eq + u disc given by s = ṡ = 0, (invariance of the sliding surface) u disc = ksign(s), (convergence in finite time onto the surface)

18 Introduction Sliding Mode Control: Advantages vs disadvantages Advantages: System order reduction Finite time convergence (adjust time response) Robustness w.r.t. parametric uncertainties and disturbances Disadvantages: Chattering phenomena (actuator damage) Noise sensitivity (??) Output feedback (??)

19 Introduction Sliding Mode Control: One more time... Sliding mode control design: hitting phase (or reaching phase), and the sliding phase. stability/attractivity concepts: existence of sliding motions is a contraction property (locally), shaping procedure: stabilization problem ( tune the shape of the sliding : in sliding minimum phase system).

20 Introduction Sliding Mode Control: One more time... { ẋ1 = x 2 (1+x 2 2 ) 2 x 1x 2 u 1+x 2 2 ẋ 2 = u (7) This system seems complex, however, if we set z 1 = x 1 (1 + x 2 2) z 2 = x 2 (note that it defines a global diffeomorphism), then one obtains

21 Introduction Sliding Mode Control: One more time... { ż1 = z 2 ż 2 = u (8) and it becomes obvious that if in sliding mode z 2 = z 1, then z 1 converges asymptotically to zero (ż 1 = z 2 = z 1 ) and thus z 2 also converges. In this step of design (the sliding phase ), the shape of the sliding manifold arises naturally.

22 Introduction Sliding Mode Control: One more time... Now, we need to force the system to evolve on the constraint z 2 = z 1. For this, let us define the sliding surface as S = {z R 2 : s(z) = 0} (9) s(z) = z 2 + z 1 (10) Then, according to the equivalent control method, we need the control to satisfy { u u(z) = + (z) if s(z) > 0 u (z) if s(z) < 0 min(u + (z), u (z)) < u eq = z 2 < max[u + (z), u (z)] in order to ensure that a sliding mode exists on S.

23 Introduction Sliding Mode Control: One more time... This leads to various design controls, for example, { 1 if s(z) > 0 u(z) = 1 if s(z) < 0 which ensures a finite time convergence to S as soon as the initial conditions are close enough to the surface and satisfy z 2 < 1. But, can we provide a better characterization of the initial conditions leading to a sliding mode?

24 Introduction Sliding Mode Control: One more time... An alternative to this control is u(z) = { z2 1 if s(z) > 0 z if s(z) < 0 (11) which ensures a finite time convergence to S, whatever the initial conditions. But since the chattering problem remains, can we stabilize the system while reducing the chattering?

25 Differential Inclusion: Notion of solution ẋ = f(x, x), x X \ S (12) where X is the state manifold (locally diffeomrophic to R n ). Problem : f is not defined on a manifold of codimension one (if S = {x R n : s(x) = 0} and s is a scalar function) thus Cauchy-Lipschitz and Peano Theorem does not apply (existence (and uniqueness) of solutions). Notion of solutions on the manifold : extend the vector field f on the manifold S. (Aizerman, Filipov, Utkin,....)

26 Differential Inclusion: Notion of solution Main points of view : Real world (system is not discontinuous), just take into account (delays, hysterisis, saturation) in a small vicinity of the sliding manifold S ε = {x R n : s(x) ε} ( ε radius), then use the usual results, then ε 0: Sliding mode are then limit of classical solution. That is Aizerman s point of view embed the discontinuous system into a Differential Inclusion (Filipov), Equivalent control theory (Utkin).

27 Differential Inclusion: Notion of solution Filipov s points of view : replace the ODE with discontinuous right-hand side ẋ = f(t, x), x X \ S R n with the following differential inclusion ẋ F (t, x) which capture the behaviors of the original system, where F (t, x) = conv(f(t, B ε (x) M)) ε>0 µ(m)=0

28 Differential Inclusion: Notion of solution DT ẋ = sign(x), x R 4 Commande 1 par mode if glissant x < 0 F (x) = 1 if x > 0 [ 1, 1] if x = 0 DX Z SIGNX X 2 SIXSIX; Z = SI X AX 2 8(%) % W. PERRUQUETTI 30 Signum

29 Differential Inclusion: Notion of solution 4 Commande par mode glissant y x S ẋ = f 0 (t, x) X - Xw F T X f 0 should be in T x S. F T X F T X F Z T X A6 4 X - f 0 (t, x) conv{f + (t, x), f (t, x)} T x S W. PERRUQUETTI 32

30 Differential Inclusion: Notion of solution f 0 = αf + + (1 α)f, α [ 1, 1] f 0 (t, x) T x S ds, f 0 = 0 α ds, f + + (1 α) ds, f = 0 α = ds, f ds, f f + ẋ = ds, f f 0 = ds, f f + f + ds, f + ds, f f + f

31 Differential Inclusion: Notion of solution Utkin s points of view : On the sliding manifold, replace the dynamics by the following ODE (equivalent dynamics) ẋ = f eq (t, x, u e q) where f eq (t, x, u e q) ensure invariance of the sliding manifold that is f eq (t, x, u e q) : s(x(t)) = 0, t > 0 thus s is identically zero which implies that ṡ is also zero Remark Filipov and Utkin thechnics are equivalent only for system linear in the control that is ẋ = f(x) + g(x)u.

32 Differential Inclusion: Notion of solution Counter example : ẋ 1 = 0.3x 2 + x 1 u (13) ẋ 2 = 0.7x 1 + 4x 1 u 3 (14) Sliding manifold defined by: s(x) = x 2 + x1 Control: u = sign(s(x)x 1 ).

33 Differential Inclusion: Notion of solution Sliding mode occurs if sṡ < 0 (close to ) : ṡ = 0.3x 2 + x 1 u 0.7x 1 + 4x 1 u 3 (15) ṡ = 0.3x 2 0.7x 1 + x 1 u(1 + 4u 2 ) (16) If s(x) 0, x 2 x 1 ṡ = x 1 + x 1 u(1 + 4u 2 ) (17) sṡ = sx 1 5 sx 1 < 0 (18) Yes sliding will occur

34 Differential Inclusion: Notion of solution Equivalent dynamics (Filipov): ( ) ( f + 0.3x2 + x (x) = 1, f 0.3x2 x (x) = 1 3.3x 1 4.7x 1 ( ) 1 1 f (x) α = ( ) ( ) = 0.3x 2 5.7x 1 2x x 1 8x 1 When x close to the sliding manifold (x 2 x 1 ) we have α = 6x 1 10x 1 = 6 10 thus the equivalent dynamics is ), (19) ẋ 1 = α(0.3x 2 + x 1 ) + (1 α)(0.3x 2 x 1 ) (20) AS = 6 10 (0.3x 2 + x 1 ) (0.3x 2 x 1 ) (21) = 0.3x x 1 = 0.1x 1 (22)

35 Differential Inclusion: Notion of solution Equivalent dynamics (Utkin): ṡ = 0.3x 2 + x 1 u 0.7x 1 + 4x 1 u 3 When x close to the sliding manifold (x 2 x 1 ) we have ṡ = x 1 + x 1 u(1 + 4u 2 ) = 0 (23) u(1 + 4u 2 ) = 1 x 1 = 0 (24) u(1 + 4u 2 ) = 1 u = 0.5, u R ẋ 1 = 0.3x x 1 When x close to the sliding manifold (x 2 x 1 ) ẋ 1 = 0.2x 1 Unstable

36 Attractivity condition and invariance condition of the sliding manifo Sliding mode equivalent dynamics Robustness with respect to matched disturbance Sliding Mode Control : First order sliding mode Non Linear affine systems ẋ = f(x) + g(x)u (25) Sliding manifold being defined by a C 1 function (same dimension as u) S = {x R n : s(x) = 0} (26)

37 Table of Contents Attractivity condition and invariance condition of the sliding manifo Sliding mode equivalent dynamics Robustness with respect to matched disturbance 1 Differential Inclusion: Notion of solution 2 Attractivity condition and invariance condition of the sliding manifold Sliding mode equivalent dynamics Robustness with respect to matched disturbance 3

38 Attractivity condition and invariance condition of the sliding manifo Sliding mode equivalent dynamics Robustness with respect to matched disturbance Sliding Mode Control : First order sliding mode Attractivity and invariance condition u = { u + if s(x) > 0 u if s(x) < 0 (27) Attractivity condition: s T ṡ < 0 min(u +, u ) < u eq < max(u +, u ) (28) Invariance condition: ṡ = 0 u = u eq (29)

39 Attractivity condition and invariance condition of the sliding manifo Sliding mode equivalent dynamics Robustness with respect to matched disturbance Sliding Mode Control : First order sliding mode Attractivity and invariance condition Be careful, this condition does not imply that the sliding manifold is reached in finite time. Thus, this condition (for the existence of a sliding mode) should be replaced by a more restrictive condition for example (mu-reachability condition) s T ṡ < µs (30) Show that V (s) = s T s goes to zero in finite time

40 Attractivity condition and invariance condition of the sliding manifo Sliding mode equivalent dynamics Robustness with respect to matched disturbance Sliding Mode Control : First order sliding mode Attractivity and invariance condition Let us consider a linear system with a linear sliding surface Equivalent control if CB invertible ẋ = Ax + Bu (31) S = {x R n : s(x) = Cx} (32) s T ṡ = s T C(Ax + Bu) < 0 (33) ṡ = 0 u eq = (CB) 1 CAx (34) If u = (CB) 1 Ksign(s) + u eq, s T ṡ = m i=1 k i s i < 0

41 Table of Contents Attractivity condition and invariance condition of the sliding manifo Sliding mode equivalent dynamics Robustness with respect to matched disturbance 1 Differential Inclusion: Notion of solution 2 Attractivity condition and invariance condition of the sliding manifold Sliding mode equivalent dynamics Robustness with respect to matched disturbance 3

42 Attractivity condition and invariance condition of the sliding manifo Sliding mode equivalent dynamics Robustness with respect to matched disturbance Sliding Mode Control : First order sliding mode Sliding mode equivalent dynamics ṡ = s x (f(x) + g(x)u) = L f s + L g su Equivalent control if L g s invertible Thus the equivalent dynamics are ṡ = 0 u eq = (L g s) 1 L f s (35) ẋ = f(x) + g(x) ( (L g s) 1 L f s ) (36) ( ( )) 1 s = Id g(x) (L g s) f(x) (37) x ( ( Id g(x) (Lg s) 1 s x)) is a projection operator

43 Attractivity condition and invariance condition of the sliding manifo Sliding mode equivalent dynamics Robustness with respect to matched disturbance Sliding Mode Control : First order sliding mode Sliding mode equivalent dynamics Let us consider a linear system ẋ = Ax + Bu (38) Equivalent control if CB invertible u eq = (CB) 1 CAx (39) ẋ = (Id B(CB) 1 C)Ax (40) = A eq x (41) A eq = (Id B(CB) 1 C)A (42)

44 Attractivity condition and invariance condition of the sliding manifo Sliding mode equivalent dynamics Robustness with respect to matched disturbance Sliding Mode Control : First order sliding mode Sliding mode equivalent dynamics Using a change of coordinates one can obtain (B 2 M m (R)) ( ) ( ) 0 A11 A B =, A = 12, C = ( ) C B 2 A 21 A 1 C ( ) A A eq = 11 A 12 C2 1 C 1A 11 C2 1 C (43) 1A 12 ( = P 1 A11 A 12 C2 1 C ) 1 A 12 P (44) 0 0 A eq has at least m zero eigenvalues and at most n m non zero ones.

45 Table of Contents Attractivity condition and invariance condition of the sliding manifo Sliding mode equivalent dynamics Robustness with respect to matched disturbance 1 Differential Inclusion: Notion of solution 2 Attractivity condition and invariance condition of the sliding manifold Sliding mode equivalent dynamics Robustness with respect to matched disturbance 3

46 Attractivity condition and invariance condition of the sliding manifo Sliding mode equivalent dynamics Robustness with respect to matched disturbance Sliding Mode Control : First order sliding mode Robustness with respect to matched disturbance ẋ = Ax + Bu + p (45) p span(b) (46) (46) is called the matching condition, thus we have p = Bp. Put (45) into a controllable canonical form (hereafter m = 1) ẋ c = A c x + B c (u + p ) (47) A c = , B c = (48) 1 a c a cn

47 Attractivity condition and invariance condition of the sliding manifo Sliding mode equivalent dynamics Robustness with respect to matched disturbance Sliding Mode Control : First order sliding mode Robustness with respect to matched disturbance Select a linear sliding manifold S = {x R n : s(x) = 0} where n 1 s(x) = x cn + a i x ci i=1 ṡ = = n i=1 n 1 a ci x ci + u + p + a i x ci+1 (49) i=1 n a cix ci + u + p, a ci = a ci + a ci 1 (50) i=1

48 Attractivity condition and invariance condition of the sliding manifo Sliding mode equivalent dynamics Robustness with respect to matched disturbance Sliding Mode Control : First order sliding mode Robustness with respect to matched disturbance Control n u = ksign(s) a cix ci (51) i=1 sṡ = k s + p s, (52) If the disturbance is bounded sup p <, then take k = µ + sup p sṡ < µ s

49 Attractivity condition and invariance condition of the sliding manifo Sliding mode equivalent dynamics Robustness with respect to matched disturbance Sliding Mode Control : First order sliding mode Robustness with respect to matched disturbance Equivalent dynamics ẋ c1 = x c2 (53). =. (54) ẋ cn 2 = x cn 1 (55) n 1 ẋ cn 1 = x cn = a i x ci (56) a i (Hurwitz) No influence of the perturbation once the sliding manifold is reached (only the hitting phase is influenced) i=1

50 Attractivity condition and invariance condition of the sliding manifo Sliding mode equivalent dynamics Robustness with respect to matched disturbance Sliding Mode Control : First order sliding mode Robustness with respect to matched disturbance Example: double integrator ẋ 1 = x 2 (57) ẋ 2 = u + p, sup p < (58) Sliding manifold: S = {x R n : s(x) = 0}, s(x) = x 2 + a 1 x 1 Compute Equivalent control (without disturbance p = 0) ṡ = 0 = u eq + a 1 x 2 u eq = a 1 x 2

51 Attractivity condition and invariance condition of the sliding manifo Sliding mode equivalent dynamics Robustness with respect to matched disturbance Sliding Mode Control : First order sliding mode Robustness with respect to matched disturbance Example: double integrator Control driving the solutions to S in finite time u = u eq + u disc, u disc = ksign(s) sṡ = s(u disc + p) < µ s, k = µ + sup p.

52 Attractivity condition and invariance condition of the sliding manifo Sliding mode equivalent dynamics Robustness with respect to matched disturbance Sliding Mode Control: First order sliding mode Advantages Insensibility against perturbations (matching perturbations) The choice of surface s(x, t) = 0 allow to choose a priori the closed-loop dynamics Disadvantages Trajectory s = 0 Chattering Chattering phenomenon s(x, t) must have a relative degree equal to 1 wrt. u The trajectories are not robust against perturbations during the reaching phase

53 Attractivity condition and invariance condition of the sliding manifo Sliding mode equivalent dynamics Robustness with respect to matched disturbance Sliding Mode Control: First order sliding mode Advantages Insensibility against perturbations (matching perturbations) The choice of surface s(x, t) = 0 allow to choose a priori the closed-loop dynamics Disadvantages Trajectory s = 0 Chattering Chattering phenomenon s(x, t) must have a relative degree equal to 1 wrt. u The trajectories are not robust against perturbations during the reaching phase

54 Higher Order Sliding Mode Control Objective Introduction Commande par modes glissants d ordre supérieur optimale Expérimentation sur deux benchmarks industriels Conclusion et perspectives To constrain the system trajectories to evolve onto the sliding surface: { } Modes S r glissants d ordre r = ρ = x R n : s = ṡ =... = s (r 1) 0 trajectoire chattering s =0 s =0 trajectoire Commande par modes Commande par modes Stabilis ż 1 ż 2 mode glissant d ordre r =1 mode glissant d ordre r > 1 ż ρ s

55 Higher Order Sliding Mode Control Introduced by A. Levant (Ph. D. supervisor Emel yanov) in 87 Ideal : { } S r = x R n : s = ṡ =... = s (r 1) = 0 Real : s = O(Ts r ) (59) ṡ = O(Ts r 1 ) (60)... =... (61) s (r 1) = O(Ts ) (62) T s = sampling period (63) With respect to a bounded deterministic Lebesgue-measurable noise (bounded by ε): s = O(ε 1/2r 1 )

56 Higher Order Sliding Mode Control Advantages: Robustness w.r.t. bounded matching perturbation, Reduce the of the sliding dynamics up to at most (n r) (in fact if counting the added integrators exactly (n r)). Finite Time convergence to S r, Chattering reduction (sometimes see relative degree of s), Higher convergence accuracy.

57 Higher Order Sliding Mode Control S r = { } x R n : s = ṡ =... = s (r 1) = 0 (64) Let the set S r be non-empty and assume that it consists of Filippov s trajectories of the discontinuous dynamic system. Definition Any motion (Filipov sense) in the set S r is called an r-sliding mode with respect to the constraint function s.

58 Higher Order Sliding Mode Control Sliding mode and relative degree ẋ = f(t, x, u), s = s(t, x) Theorem (H. Sira-Ramirez 89) A first order sliding mode exists iff the relative degree of s w.r.t the above defined system is one. Equivalent dynamics is stable system is minimum phase w.r.t s. Relative degree r strictly greater than one : Only an r-sliding mode algorithm leads to a finite time convergence on the sliding manifold.

59 Higher Order Sliding Mode Control Problem : find algorithms ensuring higher order sliding modes. There exist for r = 1, 2 and 3 for any r > 3 there no satisfactory constructive algorithm (only the structure is proposed and existence is proved for large enough parameters) Ideal Algorithms: Real Algorithms: The necessary information increase with the order Twisting and Super-twisting [Levant] Sub-optimal [Bartolini] Nested HOSM [Levant] Quasi-continuous HOSM [Levant] Good approximation for 2nd order Drift algorithm [Emel yanov] Discretized version of ideal ones

60 Higher Order Sliding Mode Control 2-order sliding mode algorithms Hypothesis: s = a(t, x) + b(t, x, u)u 1 For any continuous u(t) s.t. u U M, U M > 1 the solution of the system is well defined for all t. 2 u 1 (0, 1) s.t. for any continuous function u(t) with u(t) > u 1, t 1, s.t s(t)u(t) > 0 for each t > t 1. (u(t) = sign[s(t 0 )], enforces s = 0 in finite time) 3 s 0 > 0, u 0 < 1, Γ m > 0, Γ M > 0 such that if s(t, x) < s 0 then 0 < Γ m b(t, x, u) Γ M, u U M, x X (65) and the inequality u > u 0 entails ṡu > 0. 4 A > 0 s.t within s(t, x) < s 0 the following inequality holds t, x X, u U M a(t, x) A (66)

61 Higher Order Sliding Mode Control 2-order sliding mode algorithms: Twisting Algorithm (TA) [Levant] r(s) = 1 y 1 = s, y 2 = ṡ, after some transient a(t, x) A, 0 < Γ m b(t, x, u) Γ M, A > 0. { ẏ1 = y 2 = a(t, x) + b(t, x, u) u ẏ 2 (67) with y 2 (t) unmeasured but with a possibly known sign.

62 Higher Order Sliding Mode Control 2-order sliding mode algorithms: Twisting Algorithm (TA) [Levant] u if u > 1, u(t) = λ m sign(y 1 ) if y 1 y 2 0; u 1, λ M sign(y 1 ) if y 1 y 2 > 0; u 1. Sufficient conditions: λ M > λ m λ m > 4Γ M s0 λ m > A Γ m Γ m λ M A > Γ M λ m + A. (68) (69)

63 Higher Order Sliding Mode Control 2-order sliding mode algorithms: Twisting Algorithm (TA) [Levant]

64 Higher Order Sliding Mode Control 2-order sliding mode algorithms: Twisting Algorithm (TA) [Levant] r(s) = 2 u(t) = { λm sign(y 1 ) if y 1 y 2 0 λ M sign(y 1 ) if y 1 y 2 > 0

65 Higher Order Sliding Mode Control 2-order sliding mode algorithms: Twisting Algorithm (TA) [Levant] Example ẋ 1 = x 2 (70) ẋ 2 = x 3 (71) ẋ 3 = x 1 x 2 + u + p(t) (72) sup p(t) = π (73) t R

66 Higher Order Sliding Mode Control 2-order sliding mode algorithms: Twisting Algorithm (TA) [Levant] Example Using (70) : for s 1 (x) = x 2 + ax 1 (74) we have ṡ 1 = x 3 + ax 2, (75) s 1 = x 1 x 2 + u + p(t) + ax 3 (76) r(s 1 ) = 2, (77) thus if s 1 (x) = ṡ 1 (x) = 0 in finite time then the equiv. dynamics is ẋ 1 = ax 1 thus x 1 (t) 0, x 2 (t) 0, x 3 (t) 0.

67 Higher Order Sliding Mode Control 2-order sliding mode algorithms: Twisting Algorithm (TA) [Levant] Example Using (70) + (71) (ẋ 1 = x 2, ẋ 2 = x 3 ) : for we have s 2 (x) = x 3 + (ω 2 nx 1 + 2ζω n x 2 ) (78) ṡ 2 = x 1 x 2 + u + p(t) + (ω 2 nx 2 + 2ζω n x 3 ), (79) r(s 2 ) = 1, (80) thus if s 2 (x) = 0 in finite time then the equiv. dynamics is ẋ 1 = x 2, ẋ 2 = (ω 2 nx 1 + 2ζω n x 2 ) thus x 1 (t) 0, x 2 (t) 0, x 3 (t) 0.

68 Higher Order Sliding Mode Control 2-order sliding mode algorithms: Twisting Algorithm (TA) [Levant] Example Case 1: 1rst order SM using s 2 s 2 (x) = x 3 + (ω 2 nx 1 + 2ζω n x 2 ), ṡ 2 = x 1 x 2 + u + p(t) + (ω 2 nx 2 + 2ζω n x 3 ), Compute equiv. control (without p): u eq = x 1 x 2 (ω 2 nx 2 + 2ζω n x 3 ) u = u eq + u disc, u disc = ksign(s), k > π + µ sṡ = k s + sp < µ s

69 Higher Order Sliding Mode Control 2-order sliding mode algorithms: Twisting Algorithm (TA) [Levant] Example Case 2: 2nd order SM using s 2 Since r(s 2 ) = 1 we add : Chattering removal ẋ 1 = x 2 (81) ẋ 2 = x 3 (82) ẋ 3 = x 1 x 2 + u + p(t) (83) u = v (84)

70 Higher Order Sliding Mode Control 2-order sliding mode algorithms: Twisting Algorithm (TA) [Levant] Example Thus we have s 2 (x) = x 3 + (ωnx ζω n x 2 ), ṡ 2 = x 1 x 2 + u + p(t) + (ωnx ζω n x 3 ), s 2 = x 1 x 3 + x v + ṗ + (ωnx ζω n (x 1 x 2 + u + p(t))) = a(x) + v + (ṗ + 2ζω n p)

71 Higher Order Sliding Mode Control 2-order sliding mode algorithms: Twisting Algorithm (TA) [Levant] Example Compute equiv. control (without p): v eq = a(x) v = v eq + v disc, { λm sign(s v disc = T A(s 2 ) = 2 ) if s 2 ṡ 2 0 λ M sign(s 2 ) if s 2 ṡ 2 > 0 u = v C 0

72 Higher Order Sliding Mode Control 2-order sliding mode algorithms: Twisting Algorithm (TA) [Levant] Example Case 3: 2nd order SM using s 1 Since r(s 1 ) = 2 we can directly use TA (Chattering!!) ṡ 1 = x 3 + ax 2, (85) s 1 = x 1 x 2 + u + p(t) + ax 3 (86) Compute equiv. control (without p): v eq = x 1 x 2 ax 3 u = u eq + u disc, { λm sign(s u disc = T A(s 1 ) = 1 ) if s 1 ṡ 1 0 λ M sign(s 1 ) if s 1 ṡ 1 > 0

73 Higher Order Sliding Mode Control 2-order sliding mode algorithms: Twisting Algorithm (TA) [Levant] Convergence acceleration TA + pole placement (at the same location!!) { u = α 2 λm sign(s) if sṡ 0 s 2αṡ + λ M sign(s) if sṡ > 0

74 Higher Order Sliding Mode Control 2-order sliding mode algorithms: sub-optimal [Bartolini et al.] y 1 = s, y 2 = ṡ, after some transient a(t, x) A, 0 < Γ m b(t, x, u) Γ M, A > 0. { ẏ1 = y 2 = a(t, x) + b(t, x, u)u. ẏ 2 (87) (y 1, y 2 ) Trajectories are confined within limit parabolic arcs. Control: v(t) = α(t)λ { M sign(y 1 (t) 1 2 y 1 M ), α if [y α(t) = 1 (t) 1 2 y 1 M ][y 1M y 1 (t)] > 0 1 if [y 1 (t) 1 2 y 1 M ][y 1M y 1 (t)] 0, (88) where y 1M is the last maximum of y 1 (t), i.e. the last value of y 1 for t s.t. y 2 = ẏ 1 = 0

75 Higher Order Sliding Mode Control 2-order sliding mode algorithms: sub-optimal [Bartolini et al.] Sufficient conditions: α (0, 1] (0, 3Γm Γ M ), λ M > max ( Φ α Γ m, ) 4Φ 3Γ m α Γ M. (89)

76 Higher Order Sliding Mode Control 2-order sliding mode algorithms: Super twisting Algorithm (STA) [Levant] The control is given by: u(t) = u { 1 (t) + u 2 (t) u if u > 1 u 1 (t) = { W sign(y 1 ) if u 1 λ s0 u 2 (t) = ρ sign(y 1 ) if y 1 > s 0 λ y 1 ρ sign(y 1 ) if y 1 s 0 (90)

77 Higher Order Sliding Mode Control 2-order sliding mode algorithms: Super twisting Algorithm (STA) [Levant] Sufficient conditions : W > Φ Γ m λ 2 4A Γ 2 m 0 < ρ 1 2 Γ M (W +A) Γ m(w A) (91)

78 Higher Order Sliding Mode Control 2-order sliding mode algorithms: Super twisting Algorithm (STA) [Levant] Simplified version if b does not depend on control, u does not need to be bounded and s 0 = : u = λ s ρ sign(y 1 ) + u 1, u 1 = W sign(y 1 ).

79 Higher Order Sliding Mode Control 2-order sliding mode algorithms: Drift Algorithm (DA) [Emelyanov] Control (s relative degree is 1): u if u > 1 u = λ m sign( y 1i ) λ M sign( y 1i ) if y 1 y 1i 0; u 1 if y 1 y 1i > 0; u 1 (92) where λ m > 0, λ M > 0 are proper positive constants such that λ m < λ M and λ M λm is sufficiently large, and y 1i = y 1 (t i ) y 1 (t i τ), t [t i, t i+1 ).

80 Higher Order Sliding Mode Control 2-order sliding mode algorithms: Drift Algorithm (DA) [Emelyanov] Similar controller (when s is relative degree 2) : { λm sign( y u = 1i ) if y 1 y 1i 0 λ M sign( y 1i ) if y 1 y 1i > 0

81 Higher Order Sliding Mode Control r-order sliding mode algorithms: Hommogeneous SM [Levant] Let p least common multiple of 1, 2,..., r s (r) [ C, C] + [K m, K M ]u (93) ϕ 0,r = s (94) N 1,r = s r 1 r (95) ϕ i,r = s (i) + β i N i,r sign(ϕ i 1,r ) (96) N i,r = ( s p r s (i 1) p r i r i+1 ) p (97) u = λsign(ϕ r 1,r (s, ṡ,..., s (r) )) (98) β i hard to find but can be set in advance and λ should be large enough!

82 Higher Order Sliding Mode Control r-order sliding mode algorithms: Quasi continuous Hommogeneous SM [Levant] s (r) [ C, C] + [K m, K M ]u ϕ 0,r = s N 0,r = s Ψ 0,r = ϕ 0,r = sign(s) N 0,r ϕ i,r = s (i) r i r i r i+1 + β i N i 1,r Ψ i 1,r N i,r = s (i) r i+1 + β i N i 1,r Ψ i 1,r Ψ i,r = ϕ i,r N i,r u = λsign(ψ r 1,r (s, ṡ,..., s (r) )) β i hard to find but can be set in advance and λ should be large enough!

83 Table of Contents 1 Differential Inclusion: Notion of solution 2 3

84 Higher Order Sliding Mode Control ẋ = f(x) (99) where f is a continuous vector field or differential inclusion ẋ F (x) (100) where F is set valued map.

85 Higher Order Sliding Mode Control Sufficient condition for ODE (or DI) to be finite time stable: Lemma Suppose there exists a Lyapunov function V (x) defined on a neighborhood U R n of the origin of system (99) and some constants τ, γ > 0 and 0 < β < 1 such that d dt V (x) (99) τv (x) β + γv (x), x U\{0}. Then{ the origin of system (99) } is FTS. The set Ω = x U : V (x) 1 β < τ γ is contained in the domain of attraction of the origin. The settling time satisfies T (x) ln(1 γ τ V (x)1 β ) γ(β 1), x Ω.

86 Higher Order Sliding Mode Control Let λ > 0, r i > 0, i {1,..., n} called weights one can define: the vector of weights r = (r 1,..., r n ) T, the dilation matrix Λ r = diag{λ r i } n i=1, (101) note that Λ r x = (λ r 1 x 1,..., λ r i x i,..., λ rn x n ) T. let r denotes the finite product r 1 r 2... r n then the r homogeneous norm of x R n is defined by: n r (x) = ( x 1 r r x i r r i x n r rn ) 1 r. (102)

87 Higher Order Sliding Mode Control Definition A function h : R n R is r homogeneous with degree d r,h R if for all x R n we have (Hermes 90) : λ d r,h h(λ r x) = h(x). (103) When such a property holds, we write deg r (h) = d r,h.

88 Higher Order Sliding Mode Control Let us note that for any positive real number λ: λ 1 n r (Λ r x) = n r (x), (104) this is deg r (n r ) = 1. Let us introduce the following compact set S r = {x R n : n r (x) = 1}, (105)

89 Higher Order Sliding Mode Control Remark In fact in stead of dealing with S r one can take any closed curve properly chosen diffeomorphic to S n 1.

90 Higher Order Sliding Mode Control Such homogeneity notion can be also defined for vector fields, ordinary differential system (99) Definition A vector field f : R n R n is r homogeneous with degree d r,f R, with d r,f > min i {1,...,n} (r i ) if for all x R n we have (see Hermes 90) : λ d r,f Λ 1 r f(λ r x) = f(x), (106) which is equivalent to all i-th component f i being r homogeneous function of degree r i + d r,f. When such a property holds, we write deg r (f) = d r,f. The system (99) is r homogeneous of degree d r,f if the vector field f is homogeneous of degree d r,f.

91 Higher Order Sliding Mode Control Theorem If the system (99) is locally AS and r homogeneous with negative degree then it is FTS.

92 Higher Order Sliding Mode Control ẋ = f(x) + g(x)u, s(t, x) with r(s) = cte = ρ N +. HOSM FTS for the following system : ż 1 = z 2 ż 2 = z 3. (107) ż ρ 1 = z ρ ż ρ = a(x, t) + b(x, t)u z = [z 1, z 2,..., z ρ 1, z ρ ] T = [ s, ṡ,..., s (ρ 2), s (ρ 1)] T a(x, t) = L ρ f s(x, t) b(x, t) = L g L ρ 1 f s(x, t)

93 Higher Order Sliding Mode Control a, b have known nominal part denoted by a, b their unknown part being described by δ a, δ b, this is: { a = a + δa b = b + δ b

94 Higher Order Sliding Mode Control Assumptions: Assume that the nominal part b is invertible. Using: u = b 1 (w a) (108) where w R is the knew input (107) leads to: ż 1 = z 2 ż 2 = z 3. ż ρ 1 = z ρ ż ρ = ϑ(x, t) + (1 + ζ(x, t)) w where ϑ, ζ are given by: { ϑ = δ a δ b b 1 a ζ = δ b b 1 (109)

95 Higher Order Sliding Mode Control Assumption: ϑ(x, t), ζ(x, t) bounded: a(x) > 0 and 0 < b 1 s.t.: { ϑ(x, t) a(x) (110) ζ(x, t) 1 b Idea: FTS the unperturbed chain of integrator using homogeneity

96 Higher Order Sliding Mode Control ż 1 = z 2. ż ρ = w (111)

97 Higher Order Sliding Mode Control Theorem (Bhat 2005) Let k 1,..., k ρ positives ctes s.t. p ρ + k ρ p ρ k 2 p + k 1 is Hurwitz. Then ɛ (0, 1) s.t ν (1 ɛ, 1), (111) is FTS by: w(z) = k 1 sign (z 1 ) z 1 ν 1... k ρ sign (z ρ ) z ρ νρ (112) where ν 1,..., ν ρ are given by: with ν ρ = ν et ν ρ+1 = 1. ν i 1 = ν iν i+1 2ν i+1 ν i, i = 2,..., ρ, (113)

98 Table of Contents 1 Differential Inclusion: Notion of solution 2 3

99 Integral Sliding Mode Control Objective To remove the reaching phase To guarantee the robustness properties against perturbations in the model from the initial time instance Philosophy To choose the sliding variable such that the system trajectories are already on the sliding surface at the initial time instance

100 Integral Sliding Mode Control Objective To remove the reaching phase To guarantee the robustness properties against perturbations in the model from the initial time instance Philosophy To choose the sliding variable such that the system trajectories are already on the sliding surface at the initial time instance

101 Integral Sliding Mode Control w nom (z) FTS the unperturbed system(111). w disc (z) is built to cope with ϑ(x, t) and ζ(x, t) for (109). Leading to a ρ order sliding mode for s(x, t).

102 Table of Contents 1 Differential Inclusion: Notion of solution 2 3

103 Problem setup Differential Inclusion: Notion of solution Reference trajectory ẋ ref ẏ ref θ ref = Objective cos θ ref 0 sin θ ref [ vref w ref ] j yre f (t0) y(t0) Robot réel t1 θ t2 t4 t3 t3 t2 t1 θre f Robot de référence t4 Individual tracking of the optimal planned trajectory for each robot i To stabilize the tracking errors: e x e y e θ = x x ref y y ref θ θ ref O x(t0) xre f (t0) i Figure 1:

104 Problem setup Differential Inclusion: Notion of solution Reference trajectory ẋ ref ẏ ref θ ref = Objective cos θ ref 0 sin θ ref [ vref w ref ] j yre f (t0) y(t0) Robot réel t1 θ t2 t4 t3 t3 t2 t1 θre f Robot de référence t4 Individual tracking of the optimal planned trajectory for each robot i To stabilize the tracking errors: e x e y e θ = x x ref y y ref θ θ ref O x(t0) xre f (t0) i Figure 1:

105 Problem setup Differential Inclusion: Notion of solution Difficulties Presence of perturbations and parametric uncertainties in the model: ẋ ẏ θ = cos θ 0 sin θ [ v w ] + p(q, t)

106 Algo. 1 Differential Inclusion: Notion of solution Assumptions Perturbations satisfy the matching condition Perturbations are bounded by known positive functions Reference velocities are continuous and bounded No stop point

107 Algo. 1 Differential Inclusion: Notion of solution The tracking errors asymptotically converge toward zero under: u = u nom + u disc Continuous term u nom [Jiang et al., 2001] u nom stabilize the tracking errors without perturbation [ vref cos e 3 + µ 3 tanh e 1 u nom = w ref + µ1v ref e 2 sin e 3 1+e 2 1 +e2 2 e 3 + µ 2 tanh e 3 ] with e 1 e 2 e 3 = cos θ sin θ 0 sin θ cos θ e x e y e θ

108 Algo. 1 Differential Inclusion: Notion of solution The tracking errors asymptotically converge toward zero under: u = u nom + u disc Discontinuous term u disc u disc reject the effect of the perturbation from the initial time instance [ ] G u disc = 1 (e)sign(σ 1 ) G 2 (e)sign( e 2 σ 1 + σ 2 ) with σ = [σ 1, σ 2 ] T given by: σ = σ0 (e) + e aux σ 0 (e) = [ e 1, e 3 ] T : linear [ combinaison] of [ state vref cos e ė integral part aux = 3 1 e2 w ref 0 1 e aux = σ 0 (e(0)) ] u nom (e)

109 Algo. 1 Differential Inclusion: Notion of solution The tracking errors asymptotically converge toward zero under: u = u nom + u disc Discontinuous term u disc u disc reject the effect of the perturbation from the initial time instance [ ] G u disc = 1 (e)sign(σ 1 ) G 2 (e)sign( e 2 σ 1 + σ 2 ) with σ = [σ 1, σ 2 ] T given by: σ = σ0 (e) + e aux σ 0 (e) = [ e 1, e 3 ] T : linear [ combinaison] of [ state vref cos e ė integral part aux = 3 1 e2 w ref 0 1 e aux = σ 0 (e(0)) ] u nom (e)

110 Algo. 1 Differential Inclusion: Notion of solution The tracking errors asymptotically converge toward zero under: u = u nom + u disc Discontinuous term u disc u disc reject the effect of the perturbation from the initial time instance [ ] G u disc = 1 (e)sign(σ 1 ) G 2 (e)sign( e 2 σ 1 + σ 2 ) with σ = [σ 1, σ 2 ] T given by: σ = σ0 (e) + e aux σ 0 (e) = [ e 1, e 3 ] T : linear [ combinaison] of [ state vref cos e ė integral part aux = 3 1 e2 w ref 0 1 e aux = σ 0 (e(0)) ] u nom (e)

111 Experimental results: Algo. 1 Single nominal control 6 traj. référence traj. réelle 5 obstacle obstacle augmenté 4 ISMC 5 4 traj. référence traj. réelle obstacle obstacle augmenté y (m) x (m) y (m) erreur (m) erreur (m) t(s) t(s)

112 Algo. 1 Differential Inclusion: Notion of solution Limitations conservative assumptions discontinuities on velocities perturbations must satisfy the matching condition Solution Practical stabilization using second order ISMC x δ x(0) 2ε t δ T

113 Algo. 1 Differential Inclusion: Notion of solution Limitations conservative assumptions discontinuities on velocities perturbations must satisfy the matching condition Solution Practical stabilization using second order ISMC x δ x(0) 2ε t δ T

114 Experimental results ISM of Order 1 ISM of Order traj robot 3 traj robot 1 traj robot traj robot 2 traj robot 1 traj robot y [m] 0.2 y [m] x [m] x [m]

115 Experimental results ISM of Order 1 ISM of Order erreur l 12 l 12,des 0.14 erreur l 12 l 12,des erreur l 13 l 13,des 0.14 erreur l 13 l 13,des [m] [m] t [s] t [s] 0.8 erreur ψ 12 ψ 12,des erreur ψ 12 ψ 12,des 0.6 erreur ψ 13 ψ 13,des 0.6 erreur ψ 13 ψ 13,des [rad] 0 [rad] t [s] t [s]

116 Video Video

117 Video with 3 miabot Video

118 Video with 7 miabots Video

On homogeneity and its application in sliding mode control

On homogeneity and its application in sliding mode control On homogeneity and its application in sliding mode control Emmanuel Bernuau, Denis Efimov, Wilfrid Perruquetti, Andrey Polyakov To cite this version: Emmanuel Bernuau, Denis Efimov, Wilfrid Perruquetti,

More information

Nonlinear Control Systems

Nonlinear Control Systems Nonlinear Control Systems António Pedro Aguiar pedro@isr.ist.utl.pt 7. Feedback Linearization IST-DEEC PhD Course http://users.isr.ist.utl.pt/%7epedro/ncs1/ 1 1 Feedback Linearization Given a nonlinear

More information

High-Gain Observers in Nonlinear Feedback Control. Lecture # 3 Regulation

High-Gain Observers in Nonlinear Feedback Control. Lecture # 3 Regulation High-Gain Observers in Nonlinear Feedback Control Lecture # 3 Regulation High-Gain ObserversinNonlinear Feedback ControlLecture # 3Regulation p. 1/5 Internal Model Principle d r Servo- Stabilizing u y

More information

Sliding Mode Control à la Lyapunov

Sliding Mode Control à la Lyapunov Sliding Mode Control à la Lyapunov Jaime A. Moreno Universidad Nacional Autónoma de México Eléctrica y Computación, Instituto de Ingeniería, 04510 México D.F., Mexico, JMorenoP@ii.unam.mx 4th-8th September

More information

A. LEVANT School of Mathematical Sciences, Tel-Aviv University, Israel,

A. LEVANT School of Mathematical Sciences, Tel-Aviv University, Israel, Chapter 1 INTRODUCTION TO HIGH-ORDER SLIDING MODES A. LEVANT School of Mathematical Sciences, Tel-Aviv University, Israel, 2002-2003 1.1 Introduction One of the most important control problems is control

More information

Lecture 9 Nonlinear Control Design

Lecture 9 Nonlinear Control Design Lecture 9 Nonlinear Control Design Exact-linearization Lyapunov-based design Lab 2 Adaptive control Sliding modes control Literature: [Khalil, ch.s 13, 14.1,14.2] and [Glad-Ljung,ch.17] Course Outline

More information

An introduction to Mathematical Theory of Control

An introduction to Mathematical Theory of Control An introduction to Mathematical Theory of Control Vasile Staicu University of Aveiro UNICA, May 2018 Vasile Staicu (University of Aveiro) An introduction to Mathematical Theory of Control UNICA, May 2018

More information

Topic # /31 Feedback Control Systems. Analysis of Nonlinear Systems Lyapunov Stability Analysis

Topic # /31 Feedback Control Systems. Analysis of Nonlinear Systems Lyapunov Stability Analysis Topic # 16.30/31 Feedback Control Systems Analysis of Nonlinear Systems Lyapunov Stability Analysis Fall 010 16.30/31 Lyapunov Stability Analysis Very general method to prove (or disprove) stability of

More information

1 Lyapunov theory of stability

1 Lyapunov theory of stability M.Kawski, APM 581 Diff Equns Intro to Lyapunov theory. November 15, 29 1 1 Lyapunov theory of stability Introduction. Lyapunov s second (or direct) method provides tools for studying (asymptotic) stability

More information

LMI Methods in Optimal and Robust Control

LMI Methods in Optimal and Robust Control LMI Methods in Optimal and Robust Control Matthew M. Peet Arizona State University Lecture 15: Nonlinear Systems and Lyapunov Functions Overview Our next goal is to extend LMI s and optimization to nonlinear

More information

D(s) G(s) A control system design definition

D(s) G(s) A control system design definition R E Compensation D(s) U Plant G(s) Y Figure 7. A control system design definition x x x 2 x 2 U 2 s s 7 2 Y Figure 7.2 A block diagram representing Eq. (7.) in control form z U 2 s z Y 4 z 2 s z 2 3 Figure

More information

High-Gain Observers in Nonlinear Feedback Control

High-Gain Observers in Nonlinear Feedback Control High-Gain Observers in Nonlinear Feedback Control Lecture # 1 Introduction & Stabilization High-Gain ObserversinNonlinear Feedback ControlLecture # 1Introduction & Stabilization p. 1/4 Brief History Linear

More information

HIGHER ORDER SLIDING MODES AND ARBITRARY-ORDER EXACT ROBUST DIFFERENTIATION

HIGHER ORDER SLIDING MODES AND ARBITRARY-ORDER EXACT ROBUST DIFFERENTIATION HIGHER ORDER SLIDING MODES AND ARBITRARY-ORDER EXACT ROBUST DIFFERENTIATION A. Levant Institute for Industrial Mathematics, 4/24 Yehuda Ha-Nachtom St., Beer-Sheva 843, Israel Fax: +972-7-232 and E-mail:

More information

High order integral sliding mode control with gain adaptation

High order integral sliding mode control with gain adaptation 3 European Control Conference (ECC) July 7-9, 3, Zürich, Switzerland. High order integral sliding mode control with gain adaptation M. Taleb, F. Plestan, and B. Bououlid Abstract In this paper, an adaptive

More information

EN Nonlinear Control and Planning in Robotics Lecture 3: Stability February 4, 2015

EN Nonlinear Control and Planning in Robotics Lecture 3: Stability February 4, 2015 EN530.678 Nonlinear Control and Planning in Robotics Lecture 3: Stability February 4, 2015 Prof: Marin Kobilarov 0.1 Model prerequisites Consider ẋ = f(t, x). We will make the following basic assumptions

More information

Stabilization and Passivity-Based Control

Stabilization and Passivity-Based Control DISC Systems and Control Theory of Nonlinear Systems, 2010 1 Stabilization and Passivity-Based Control Lecture 8 Nonlinear Dynamical Control Systems, Chapter 10, plus handout from R. Sepulchre, Constructive

More information

A higher order sliding mode controller for a class of MIMO nonlinear systems: application to PM synchronous motor control

A higher order sliding mode controller for a class of MIMO nonlinear systems: application to PM synchronous motor control A higher order sliding mode controller for a class of MIMO nonlinear systems: application to PM synchronous motor control S Laghrouche, F Plestan and A Glumineau Abstract A new robust higher order sliding

More information

Higher order sliding mode control based on adaptive first order sliding mode controller

Higher order sliding mode control based on adaptive first order sliding mode controller Preprints of the 19th World Congress The International Federation of Automatic Control Cape Town, South Africa. August 4-9, 14 Higher order sliding mode control based on adaptive first order sliding mode

More information

Stability and Robustness of Homogeneous Differential Inclusions

Stability and Robustness of Homogeneous Differential Inclusions Stability and Robustness of Homogeneous Differential Inclusions Arie Levant 1, Denis Efimov 23, Andrey Polyakov 23, Wilfrid Perruquetti 2 Abstract The known results on asymptotic stability of homogeneous

More information

I. D. Landau, A. Karimi: A Course on Adaptive Control Adaptive Control. Part 9: Adaptive Control with Multiple Models and Switching

I. D. Landau, A. Karimi: A Course on Adaptive Control Adaptive Control. Part 9: Adaptive Control with Multiple Models and Switching I. D. Landau, A. Karimi: A Course on Adaptive Control - 5 1 Adaptive Control Part 9: Adaptive Control with Multiple Models and Switching I. D. Landau, A. Karimi: A Course on Adaptive Control - 5 2 Outline

More information

Lecture 8. Chapter 5: Input-Output Stability Chapter 6: Passivity Chapter 14: Passivity-Based Control. Eugenio Schuster.

Lecture 8. Chapter 5: Input-Output Stability Chapter 6: Passivity Chapter 14: Passivity-Based Control. Eugenio Schuster. Lecture 8 Chapter 5: Input-Output Stability Chapter 6: Passivity Chapter 14: Passivity-Based Control Eugenio Schuster schuster@lehigh.edu Mechanical Engineering and Mechanics Lehigh University Lecture

More information

Chap. 3. Controlled Systems, Controllability

Chap. 3. Controlled Systems, Controllability Chap. 3. Controlled Systems, Controllability 1. Controllability of Linear Systems 1.1. Kalman s Criterion Consider the linear system ẋ = Ax + Bu where x R n : state vector and u R m : input vector. A :

More information

CDS 101/110a: Lecture 2.1 Dynamic Behavior

CDS 101/110a: Lecture 2.1 Dynamic Behavior CDS 11/11a: Lecture 2.1 Dynamic Behavior Richard M. Murray 6 October 28 Goals: Learn to use phase portraits to visualize behavior of dynamical systems Understand different types of stability for an equilibrium

More information

Controls Problems for Qualifying Exam - Spring 2014

Controls Problems for Qualifying Exam - Spring 2014 Controls Problems for Qualifying Exam - Spring 2014 Problem 1 Consider the system block diagram given in Figure 1. Find the overall transfer function T(s) = C(s)/R(s). Note that this transfer function

More information

CONTROL OF THE NONHOLONOMIC INTEGRATOR

CONTROL OF THE NONHOLONOMIC INTEGRATOR June 6, 25 CONTROL OF THE NONHOLONOMIC INTEGRATOR R. N. Banavar (Work done with V. Sankaranarayanan) Systems & Control Engg. Indian Institute of Technology, Bombay Mumbai -INDIA. banavar@iitb.ac.in Outline

More information

Introduction to Nonlinear Control Lecture # 3 Time-Varying and Perturbed Systems

Introduction to Nonlinear Control Lecture # 3 Time-Varying and Perturbed Systems p. 1/5 Introduction to Nonlinear Control Lecture # 3 Time-Varying and Perturbed Systems p. 2/5 Time-varying Systems ẋ = f(t, x) f(t, x) is piecewise continuous in t and locally Lipschitz in x for all t

More information

Chapter 3 HIGHER ORDER SLIDING MODES L. FRIDMAN Samara Architecture and Civil Engineering Academy, Samara, Russia Tel.: (7) , Fax: (7) 846.

Chapter 3 HIGHER ORDER SLIDING MODES L. FRIDMAN Samara Architecture and Civil Engineering Academy, Samara, Russia Tel.: (7) , Fax: (7) 846. Chapter 3 HIGHER ORDER SLIDING MODES L. FRIDMAN Samara Architecture and Civil Engineering Academy, Samara, Russia Tel.: (7) 846.2334237, Fax: (7) 846.2421228 E-mail: fridman@info.ssu.samara.ru A. LEVANT

More information

A sub-optimal second order sliding mode controller for systems with saturating actuators

A sub-optimal second order sliding mode controller for systems with saturating actuators 28 American Control Conference Westin Seattle Hotel, Seattle, Washington, USA June -3, 28 FrB2.5 A sub-optimal second order sliding mode for systems with saturating actuators Antonella Ferrara and Matteo

More information

Every real system has uncertainties, which include system parametric uncertainties, unmodeled dynamics

Every real system has uncertainties, which include system parametric uncertainties, unmodeled dynamics Sensitivity Analysis of Disturbance Accommodating Control with Kalman Filter Estimation Jemin George and John L. Crassidis University at Buffalo, State University of New York, Amherst, NY, 14-44 The design

More information

High-Gain Observers in Nonlinear Feedback Control. Lecture # 2 Separation Principle

High-Gain Observers in Nonlinear Feedback Control. Lecture # 2 Separation Principle High-Gain Observers in Nonlinear Feedback Control Lecture # 2 Separation Principle High-Gain ObserversinNonlinear Feedback ControlLecture # 2Separation Principle p. 1/4 The Class of Systems ẋ = Ax + Bφ(x,

More information

EEE 184: Introduction to feedback systems

EEE 184: Introduction to feedback systems EEE 84: Introduction to feedback systems Summary 6 8 8 x 7 7 6 Level() 6 5 4 4 5 5 time(s) 4 6 8 Time (seconds) Fig.. Illustration of BIBO stability: stable system (the input is a unit step) Fig.. step)

More information

1 The Observability Canonical Form

1 The Observability Canonical Form NONLINEAR OBSERVERS AND SEPARATION PRINCIPLE 1 The Observability Canonical Form In this Chapter we discuss the design of observers for nonlinear systems modelled by equations of the form ẋ = f(x, u) (1)

More information

Prof. Krstic Nonlinear Systems MAE281A Homework set 1 Linearization & phase portrait

Prof. Krstic Nonlinear Systems MAE281A Homework set 1 Linearization & phase portrait Prof. Krstic Nonlinear Systems MAE28A Homework set Linearization & phase portrait. For each of the following systems, find all equilibrium points and determine the type of each isolated equilibrium. Use

More information

CDS 101/110a: Lecture 2.1 Dynamic Behavior

CDS 101/110a: Lecture 2.1 Dynamic Behavior CDS 11/11a: Lecture.1 Dynamic Behavior Richard M. Murray 6 October 8 Goals: Learn to use phase portraits to visualize behavior of dynamical systems Understand different types of stability for an equilibrium

More information

Input to state Stability

Input to state Stability Input to state Stability Mini course, Universität Stuttgart, November 2004 Lars Grüne, Mathematisches Institut, Universität Bayreuth Part IV: Applications ISS Consider with solutions ϕ(t, x, w) ẋ(t) =

More information

Design of Sliding Mode Control for Nonlinear Uncertain System

Design of Sliding Mode Control for Nonlinear Uncertain System Design of Sliding Mode Control for Nonlinear Uncertain System 1 Yogita Pimpale, 2 Dr.B.J.Parvat ME student,instrumentation and Control Engineering,P.R.E.C. Loni,Ahmednagar, Maharashtra,India Associate

More information

Feedback Linearization

Feedback Linearization Feedback Linearization Peter Al Hokayem and Eduardo Gallestey May 14, 2015 1 Introduction Consider a class o single-input-single-output (SISO) nonlinear systems o the orm ẋ = (x) + g(x)u (1) y = h(x) (2)

More information

Robust Stabilization of Non-Minimum Phase Nonlinear Systems Using Extended High Gain Observers

Robust Stabilization of Non-Minimum Phase Nonlinear Systems Using Extended High Gain Observers 28 American Control Conference Westin Seattle Hotel, Seattle, Washington, USA June 11-13, 28 WeC15.1 Robust Stabilization of Non-Minimum Phase Nonlinear Systems Using Extended High Gain Observers Shahid

More information

Applied Math Qualifying Exam 11 October Instructions: Work 2 out of 3 problems in each of the 3 parts for a total of 6 problems.

Applied Math Qualifying Exam 11 October Instructions: Work 2 out of 3 problems in each of the 3 parts for a total of 6 problems. Printed Name: Signature: Applied Math Qualifying Exam 11 October 2014 Instructions: Work 2 out of 3 problems in each of the 3 parts for a total of 6 problems. 2 Part 1 (1) Let Ω be an open subset of R

More information

A Model-Free Control System Based on the Sliding Mode Control Method with Applications to Multi-Input-Multi-Output Systems

A Model-Free Control System Based on the Sliding Mode Control Method with Applications to Multi-Input-Multi-Output Systems Proceedings of the 4 th International Conference of Control, Dynamic Systems, and Robotics (CDSR'17) Toronto, Canada August 21 23, 2017 Paper No. 119 DOI: 10.11159/cdsr17.119 A Model-Free Control System

More information

Computing Optimized Nonlinear Sliding Surfaces

Computing Optimized Nonlinear Sliding Surfaces Computing Optimized Nonlinear Sliding Surfaces Azad Ghaffari and Mohammad Javad Yazdanpanah Abstract In this paper, we have concentrated on real systems consisting of structural uncertainties and affected

More information

Chapter 3 HIGHER ORDER SLIDING MODES. L. FRIDMAN and A. LEVANT. Chihuahua Institute of Technology, Chihuahua, Mexico.

Chapter 3 HIGHER ORDER SLIDING MODES. L. FRIDMAN and A. LEVANT. Chihuahua Institute of Technology, Chihuahua, Mexico. Chapter 3 HIGHER ORDER SLIDING MODES L. FRIDMAN and A. LEVANT Chihuahua Institute of Technology, Chihuahua, Mexico. Institute for Industrial Mathematics, Beer-Sheva, Israel. 3.1 Introduction One of the

More information

Navigation and Obstacle Avoidance via Backstepping for Mechanical Systems with Drift in the Closed Loop

Navigation and Obstacle Avoidance via Backstepping for Mechanical Systems with Drift in the Closed Loop Navigation and Obstacle Avoidance via Backstepping for Mechanical Systems with Drift in the Closed Loop Jan Maximilian Montenbruck, Mathias Bürger, Frank Allgöwer Abstract We study backstepping controllers

More information

Stabilization of persistently excited linear systems

Stabilization of persistently excited linear systems Stabilization of persistently excited linear systems Yacine Chitour Laboratoire des signaux et systèmes & Université Paris-Sud, Orsay Exposé LJLL Paris, 28/9/2012 Stabilization & intermittent control Consider

More information

Observability for deterministic systems and high-gain observers

Observability for deterministic systems and high-gain observers Observability for deterministic systems and high-gain observers design. Part 1. March 29, 2011 Introduction and problem description Definition of observability Consequences of instantaneous observability

More information

Global stabilization of feedforward systems with exponentially unstable Jacobian linearization

Global stabilization of feedforward systems with exponentially unstable Jacobian linearization Global stabilization of feedforward systems with exponentially unstable Jacobian linearization F Grognard, R Sepulchre, G Bastin Center for Systems Engineering and Applied Mechanics Université catholique

More information

Convergence Rate of Nonlinear Switched Systems

Convergence Rate of Nonlinear Switched Systems Convergence Rate of Nonlinear Switched Systems Philippe JOUAN and Saïd NACIRI arxiv:1511.01737v1 [math.oc] 5 Nov 2015 January 23, 2018 Abstract This paper is concerned with the convergence rate of the

More information

Modeling and Analysis of Dynamic Systems

Modeling and Analysis of Dynamic Systems Modeling and Analysis of Dynamic Systems Dr. Guillaume Ducard Fall 2017 Institute for Dynamic Systems and Control ETH Zurich, Switzerland G. Ducard c 1 / 57 Outline 1 Lecture 13: Linear System - Stability

More information

Zeros and zero dynamics

Zeros and zero dynamics CHAPTER 4 Zeros and zero dynamics 41 Zero dynamics for SISO systems Consider a linear system defined by a strictly proper scalar transfer function that does not have any common zero and pole: g(s) =α p(s)

More information

Autonomous Helicopter Landing A Nonlinear Output Regulation Perspective

Autonomous Helicopter Landing A Nonlinear Output Regulation Perspective Autonomous Helicopter Landing A Nonlinear Output Regulation Perspective Andrea Serrani Department of Electrical and Computer Engineering Collaborative Center for Control Sciences The Ohio State University

More information

CDS Solutions to Final Exam

CDS Solutions to Final Exam CDS 22 - Solutions to Final Exam Instructor: Danielle C Tarraf Fall 27 Problem (a) We will compute the H 2 norm of G using state-space methods (see Section 26 in DFT) We begin by finding a minimal state-space

More information

Stability of Feedback Solutions for Infinite Horizon Noncooperative Differential Games

Stability of Feedback Solutions for Infinite Horizon Noncooperative Differential Games Stability of Feedback Solutions for Infinite Horizon Noncooperative Differential Games Alberto Bressan ) and Khai T. Nguyen ) *) Department of Mathematics, Penn State University **) Department of Mathematics,

More information

Entrance Exam, Differential Equations April, (Solve exactly 6 out of the 8 problems) y + 2y + y cos(x 2 y) = 0, y(0) = 2, y (0) = 4.

Entrance Exam, Differential Equations April, (Solve exactly 6 out of the 8 problems) y + 2y + y cos(x 2 y) = 0, y(0) = 2, y (0) = 4. Entrance Exam, Differential Equations April, 7 (Solve exactly 6 out of the 8 problems). Consider the following initial value problem: { y + y + y cos(x y) =, y() = y. Find all the values y such that the

More information

Nonlinear Control Lecture 9: Feedback Linearization

Nonlinear Control Lecture 9: Feedback Linearization Nonlinear Control Lecture 9: Feedback Linearization Farzaneh Abdollahi Department of Electrical Engineering Amirkabir University of Technology Fall 2011 Farzaneh Abdollahi Nonlinear Control Lecture 9 1/75

More information

Energy-based Swing-up of the Acrobot and Time-optimal Motion

Energy-based Swing-up of the Acrobot and Time-optimal Motion Energy-based Swing-up of the Acrobot and Time-optimal Motion Ravi N. Banavar Systems and Control Engineering Indian Institute of Technology, Bombay Mumbai-476, India Email: banavar@ee.iitb.ac.in Telephone:(91)-(22)

More information

Tracking Control of a Class of Differential Inclusion Systems via Sliding Mode Technique

Tracking Control of a Class of Differential Inclusion Systems via Sliding Mode Technique International Journal of Automation and Computing (3), June 24, 38-32 DOI: 7/s633-4-793-6 Tracking Control of a Class of Differential Inclusion Systems via Sliding Mode Technique Lei-Po Liu Zhu-Mu Fu Xiao-Na

More information

How to Implement Super-Twisting Controller based on Sliding Mode Observer?

How to Implement Super-Twisting Controller based on Sliding Mode Observer? How to Implement Super-Twisting Controller based on Sliding Mode Observer? Asif Chalanga 1 Shyam Kamal 2 Prof.L.Fridman 3 Prof.B.Bandyopadhyay 4 and Prof.J.A.Moreno 5 124 Indian Institute of Technology

More information

Lecture 7. Please note. Additional tutorial. Please note that there is no lecture on Tuesday, 15 November 2011.

Lecture 7. Please note. Additional tutorial. Please note that there is no lecture on Tuesday, 15 November 2011. Lecture 7 3 Ordinary differential equations (ODEs) (continued) 6 Linear equations of second order 7 Systems of differential equations Please note Please note that there is no lecture on Tuesday, 15 November

More information

Lecture 2: Controllability of nonlinear systems

Lecture 2: Controllability of nonlinear systems DISC Systems and Control Theory of Nonlinear Systems 1 Lecture 2: Controllability of nonlinear systems Nonlinear Dynamical Control Systems, Chapter 3 See www.math.rug.nl/ arjan (under teaching) for info

More information

Introduction to Nonlinear Control Lecture # 4 Passivity

Introduction to Nonlinear Control Lecture # 4 Passivity p. 1/6 Introduction to Nonlinear Control Lecture # 4 Passivity È p. 2/6 Memoryless Functions ¹ y È Ý Ù È È È È u (b) µ power inflow = uy Resistor is passive if uy 0 p. 3/6 y y y u u u (a) (b) (c) Passive

More information

Massachusetts Institute of Technology. Department of Electrical Engineering and Computer Science : MULTIVARIABLE CONTROL SYSTEMS by A.

Massachusetts Institute of Technology. Department of Electrical Engineering and Computer Science : MULTIVARIABLE CONTROL SYSTEMS by A. Massachusetts Institute of Technology Department of Electrical Engineering and Computer Science 6.245: MULTIVARIABLE CONTROL SYSTEMS by A. Megretski Q-Parameterization 1 This lecture introduces the so-called

More information

Introduction. Performance and Robustness (Chapter 1) Advanced Control Systems Spring / 31

Introduction. Performance and Robustness (Chapter 1) Advanced Control Systems Spring / 31 Introduction Classical Control Robust Control u(t) y(t) G u(t) G + y(t) G : nominal model G = G + : plant uncertainty Uncertainty sources : Structured : parametric uncertainty, multimodel uncertainty Unstructured

More information

Nonlinear Control Systems

Nonlinear Control Systems Nonlinear Control Systems António Pedro Aguiar pedro@isr.ist.utl.pt 3. Fundamental properties IST-DEEC PhD Course http://users.isr.ist.utl.pt/%7epedro/ncs2012/ 2012 1 Example Consider the system ẋ = f

More information

Sliding mode control of continuous time systems with reaching law based on exponential function

Sliding mode control of continuous time systems with reaching law based on exponential function Journal of Physics: Conference Series PAPER OPEN ACCESS Sliding mode control of continuous time systems with reaching law based on exponential function To cite this article: Piotr Gamorski 15 J. Phys.:

More information

Feedback Linearization based Arc Length Control for Gas Metal Arc Welding

Feedback Linearization based Arc Length Control for Gas Metal Arc Welding 5 American Control Conference June 8-, 5. Portland, OR, USA FrA5.6 Feedback Linearization based Arc Length Control for Gas Metal Arc Welding Jesper S. Thomsen Abstract In this paper a feedback linearization

More information

Higher Order Sliding Mode Control: A Control Lyapunov Function Based Approach

Higher Order Sliding Mode Control: A Control Lyapunov Function Based Approach Higher Order Sliding Mode Control: A Control Lyapunov Function Based Approach Shyam Kamal IIT Bombay Systems and Control Engg. CRNTS Building, Powai, Mumbai India shyam@sc.iitb.ac.in B. Bandyopadhyay IIT

More information

MCE693/793: Analysis and Control of Nonlinear Systems

MCE693/793: Analysis and Control of Nonlinear Systems MCE693/793: Analysis and Control of Nonlinear Systems Input-Output and Input-State Linearization Zero Dynamics of Nonlinear Systems Hanz Richter Mechanical Engineering Department Cleveland State University

More information

Exam. 135 minutes, 15 minutes reading time

Exam. 135 minutes, 15 minutes reading time Exam August 6, 208 Control Systems II (5-0590-00) Dr. Jacopo Tani Exam Exam Duration: 35 minutes, 5 minutes reading time Number of Problems: 35 Number of Points: 47 Permitted aids: 0 pages (5 sheets) A4.

More information

Global Analysis of Piecewise Linear Systems Using Impact Maps and Quadratic Surface Lyapunov Functions

Global Analysis of Piecewise Linear Systems Using Impact Maps and Quadratic Surface Lyapunov Functions Global Analysis of Piecewise Linear Systems Using Impact Maps and Quadratic Surface Lyapunov Functions Jorge M. Gonçalves, Alexandre Megretski, Munther A. Dahleh Department of EECS, Room 35-41 MIT, Cambridge,

More information

Second Order Sliding Mode Control for Nonlinear Affine Systems with Quantized Uncertainty

Second Order Sliding Mode Control for Nonlinear Affine Systems with Quantized Uncertainty Second Order Sliding Mode Control for Nonlinear Affine Systems with Quantized Uncertainty Gian Paolo Incremona a, Michele Cucuzzella b, Antonella Ferrara b a Dipartimento di Elettronica, Informazione e

More information

Nonlinear Control Systems

Nonlinear Control Systems Nonlinear Control Systems António Pedro Aguiar pedro@isr.ist.utl.pt 5. Input-Output Stability DEEC PhD Course http://users.isr.ist.utl.pt/%7epedro/ncs2012/ 2012 1 Input-Output Stability y = Hu H denotes

More information

State Regulator. Advanced Control. design of controllers using pole placement and LQ design rules

State Regulator. Advanced Control. design of controllers using pole placement and LQ design rules Advanced Control State Regulator Scope design of controllers using pole placement and LQ design rules Keywords pole placement, optimal control, LQ regulator, weighting matrixes Prerequisites Contact state

More information

An introduction to Birkhoff normal form

An introduction to Birkhoff normal form An introduction to Birkhoff normal form Dario Bambusi Dipartimento di Matematica, Universitá di Milano via Saldini 50, 0133 Milano (Italy) 19.11.14 1 Introduction The aim of this note is to present an

More information

Third In-Class Exam Solutions Math 246, Professor David Levermore Thursday, 3 December 2009 (1) [6] Given that 2 is an eigenvalue of the matrix

Third In-Class Exam Solutions Math 246, Professor David Levermore Thursday, 3 December 2009 (1) [6] Given that 2 is an eigenvalue of the matrix Third In-Class Exam Solutions Math 26, Professor David Levermore Thursday, December 2009 ) [6] Given that 2 is an eigenvalue of the matrix A 2, 0 find all the eigenvectors of A associated with 2. Solution.

More information

Author's Accepted Manuscript

Author's Accepted Manuscript Author's Accepted Manuscript Stability notions and lyapunov functions for sliding mode control systems Andrey Polyakov, Leonid Fridman PII: DOI: Reference: To appear in: S0016-0032(14)00004-0 http://dx.doi.org/10.1016/j.jfranklin.2014.01.002

More information

1 Relative degree and local normal forms

1 Relative degree and local normal forms THE ZERO DYNAMICS OF A NONLINEAR SYSTEM 1 Relative degree and local normal orms The purpose o this Section is to show how single-input single-output nonlinear systems can be locally given, by means o a

More information

Lecture 9 Nonlinear Control Design. Course Outline. Exact linearization: example [one-link robot] Exact Feedback Linearization

Lecture 9 Nonlinear Control Design. Course Outline. Exact linearization: example [one-link robot] Exact Feedback Linearization Lecture 9 Nonlinear Control Design Course Outline Eact-linearization Lyapunov-based design Lab Adaptive control Sliding modes control Literature: [Khalil, ch.s 13, 14.1,14.] and [Glad-Ljung,ch.17] Lecture

More information

Automatic Control 2. Loop shaping. Prof. Alberto Bemporad. University of Trento. Academic year

Automatic Control 2. Loop shaping. Prof. Alberto Bemporad. University of Trento. Academic year Automatic Control 2 Loop shaping Prof. Alberto Bemporad University of Trento Academic year 21-211 Prof. Alberto Bemporad (University of Trento) Automatic Control 2 Academic year 21-211 1 / 39 Feedback

More information

Gramians based model reduction for hybrid switched systems

Gramians based model reduction for hybrid switched systems Gramians based model reduction for hybrid switched systems Y. Chahlaoui Younes.Chahlaoui@manchester.ac.uk Centre for Interdisciplinary Computational and Dynamical Analysis (CICADA) School of Mathematics

More information

Robust discrete time control

Robust discrete time control Robust discrete time control I.D. Landau Emeritus Research Director at C.N.R. Laboratoire d utomatique de Grenoble, INPG/CNR, France pril 2004, Valencia I.D. Landau course on robust discrete time control,

More information

Feedback Refinement Relations for the Synthesis of Symbolic Controllers

Feedback Refinement Relations for the Synthesis of Symbolic Controllers Feedback Refinement Relations for the Synthesis of Symbolic Controllers Gunther Reissig 1, Alexander Weber 1 and Matthias Rungger 2 1: Chair of Control Engineering Universität der Bundeswehr, München 2:

More information

CONTROL DESIGN FOR SET POINT TRACKING

CONTROL DESIGN FOR SET POINT TRACKING Chapter 5 CONTROL DESIGN FOR SET POINT TRACKING In this chapter, we extend the pole placement, observer-based output feedback design to solve tracking problems. By tracking we mean that the output is commanded

More information

Homogeneous High-Order Sliding Modes

Homogeneous High-Order Sliding Modes Homogeneous High-Order Sliding Modes A. Levant* * Applied Mathematics Department, Tel-Aviv University, Tel-Aviv, Israel, (e-mail: levant@post.tau.ac.il) Abstract: Homogeneity features of dynamic systems

More information

DISCRETE-TIME TIME-VARYING ROBUST STABILIZATION FOR SYSTEMS IN POWER FORM. Dina Shona Laila and Alessandro Astolfi

DISCRETE-TIME TIME-VARYING ROBUST STABILIZATION FOR SYSTEMS IN POWER FORM. Dina Shona Laila and Alessandro Astolfi DISCRETE-TIME TIME-VARYING ROBUST STABILIZATION FOR SYSTEMS IN POWER FORM Dina Shona Laila and Alessandro Astolfi Electrical and Electronic Engineering Department Imperial College, Exhibition Road, London

More information

Nonlinear Observers. Jaime A. Moreno. Eléctrica y Computación Instituto de Ingeniería Universidad Nacional Autónoma de México

Nonlinear Observers. Jaime A. Moreno. Eléctrica y Computación Instituto de Ingeniería Universidad Nacional Autónoma de México Nonlinear Observers Jaime A. Moreno JMorenoP@ii.unam.mx Eléctrica y Computación Instituto de Ingeniería Universidad Nacional Autónoma de México XVI Congreso Latinoamericano de Control Automático October

More information

2 Statement of the problem and assumptions

2 Statement of the problem and assumptions Mathematical Notes, 25, vol. 78, no. 4, pp. 466 48. Existence Theorem for Optimal Control Problems on an Infinite Time Interval A.V. Dmitruk and N.V. Kuz kina We consider an optimal control problem on

More information

Dynamical systems with Gaussian and Levy noise: analytical and stochastic approaches

Dynamical systems with Gaussian and Levy noise: analytical and stochastic approaches Dynamical systems with Gaussian and Levy noise: analytical and stochastic approaches Noise is often considered as some disturbing component of the system. In particular physical situations, noise becomes

More information

Theorem 1. ẋ = Ax is globally exponentially stable (GES) iff A is Hurwitz (i.e., max(re(σ(a))) < 0).

Theorem 1. ẋ = Ax is globally exponentially stable (GES) iff A is Hurwitz (i.e., max(re(σ(a))) < 0). Linear Systems Notes Lecture Proposition. A M n (R) is positive definite iff all nested minors are greater than or equal to zero. n Proof. ( ): Positive definite iff λ i >. Let det(a) = λj and H = {x D

More information

EL 625 Lecture 10. Pole Placement and Observer Design. ẋ = Ax (1)

EL 625 Lecture 10. Pole Placement and Observer Design. ẋ = Ax (1) EL 625 Lecture 0 EL 625 Lecture 0 Pole Placement and Observer Design Pole Placement Consider the system ẋ Ax () The solution to this system is x(t) e At x(0) (2) If the eigenvalues of A all lie in the

More information

Stabilization in spite of matched unmodelled dynamics and An equivalent definition of input-to-state stability

Stabilization in spite of matched unmodelled dynamics and An equivalent definition of input-to-state stability Stabilization in spite of matched unmodelled dynamics and An equivalent definition of input-to-state stability Laurent Praly Centre Automatique et Systèmes École des Mines de Paris 35 rue St Honoré 7735

More information

1 (30 pts) Dominant Pole

1 (30 pts) Dominant Pole EECS C8/ME C34 Fall Problem Set 9 Solutions (3 pts) Dominant Pole For the following transfer function: Y (s) U(s) = (s + )(s + ) a) Give state space description of the system in parallel form (ẋ = Ax +

More information

Nonlinear Control. Nonlinear Control Lecture # 8 Time Varying and Perturbed Systems

Nonlinear Control. Nonlinear Control Lecture # 8 Time Varying and Perturbed Systems Nonlinear Control Lecture # 8 Time Varying and Perturbed Systems Time-varying Systems ẋ = f(t,x) f(t,x) is piecewise continuous in t and locally Lipschitz in x for all t 0 and all x D, (0 D). The origin

More information

Power Rate Reaching Law Based Second Order Sliding Mode Control

Power Rate Reaching Law Based Second Order Sliding Mode Control International OPEN ACCESS Journal Of Modern Engineering Research (IJMER) Power Rate Reaching Law Based Second Order Sliding Mode Control Nikam A.E 1. Sankeshwari S.S 2. 1 P.G. Department. (Electrical Control

More information

CHATTERING-FREE SMC WITH UNIDIRECTIONAL AUXILIARY SURFACES FOR NONLINEAR SYSTEM WITH STATE CONSTRAINTS. Jian Fu, Qing-Xian Wu and Ze-Hui Mao

CHATTERING-FREE SMC WITH UNIDIRECTIONAL AUXILIARY SURFACES FOR NONLINEAR SYSTEM WITH STATE CONSTRAINTS. Jian Fu, Qing-Xian Wu and Ze-Hui Mao International Journal of Innovative Computing, Information and Control ICIC International c 2013 ISSN 1349-4198 Volume 9, Number 12, December 2013 pp. 4793 4809 CHATTERING-FREE SMC WITH UNIDIRECTIONAL

More information

1. Find the solution of the following uncontrolled linear system. 2 α 1 1

1. Find the solution of the following uncontrolled linear system. 2 α 1 1 Appendix B Revision Problems 1. Find the solution of the following uncontrolled linear system 0 1 1 ẋ = x, x(0) =. 2 3 1 Class test, August 1998 2. Given the linear system described by 2 α 1 1 ẋ = x +

More information

Minimum-Phase Property of Nonlinear Systems in Terms of a Dissipation Inequality

Minimum-Phase Property of Nonlinear Systems in Terms of a Dissipation Inequality Minimum-Phase Property of Nonlinear Systems in Terms of a Dissipation Inequality Christian Ebenbauer Institute for Systems Theory in Engineering, University of Stuttgart, 70550 Stuttgart, Germany ce@ist.uni-stuttgart.de

More information

Nonlinear Control Lecture # 14 Tracking & Regulation. Nonlinear Control

Nonlinear Control Lecture # 14 Tracking & Regulation. Nonlinear Control Nonlinear Control Lecture # 14 Tracking & Regulation Normal form: η = f 0 (η,ξ) ξ i = ξ i+1, for 1 i ρ 1 ξ ρ = a(η,ξ)+b(η,ξ)u y = ξ 1 η D η R n ρ, ξ = col(ξ 1,...,ξ ρ ) D ξ R ρ Tracking Problem: Design

More information

Robust Semiglobal Nonlinear Output Regulation The case of systems in triangular form

Robust Semiglobal Nonlinear Output Regulation The case of systems in triangular form Robust Semiglobal Nonlinear Output Regulation The case of systems in triangular form Andrea Serrani Department of Electrical and Computer Engineering Collaborative Center for Control Sciences The Ohio

More information

Chaos suppression of uncertain gyros in a given finite time

Chaos suppression of uncertain gyros in a given finite time Chin. Phys. B Vol. 1, No. 11 1 1155 Chaos suppression of uncertain gyros in a given finite time Mohammad Pourmahmood Aghababa a and Hasan Pourmahmood Aghababa bc a Electrical Engineering Department, Urmia

More information

7 Planar systems of linear ODE

7 Planar systems of linear ODE 7 Planar systems of linear ODE Here I restrict my attention to a very special class of autonomous ODE: linear ODE with constant coefficients This is arguably the only class of ODE for which explicit solution

More information