A novel principle for relay-based autotuning

Transcription

1 A novel principle for relay-based autotuning Roman Prokop, Jiří orbel, and Ondrej Líška Abstract his paper presents a new simple principle for aperiodic tuning of SISO controllers used in autotuning schemes. Autotuners represent a combination of relay feedback identification and some control design method. In this contribution, models with up to three parameters are estimated by means of a single asymmetrical relay experiment. hen a stable low order transfer function is identified. Subsequently, the controller is analytically derived from general solutions of Diophantine equations in the ring of proper and stable rational functions RPS. his approach enables to define a scalar positive parameter through a pole-placement root of the characteristic closed loop equation. A first order identification yields a PI-like controllers while a second order identification generates PID ones. he analytical simple rule is derived for aperiodic control response and the scalar tuning parameter m> is then tuned according to identified time constant of an approximated transfer function. eywords autotuning, algebraic control design, relay experiment, pole-placement problem. I. INRODUCION Industrial processes are usually controlled by PID controllers, Yu in [] refers that more than 97 % of control loops are of this type and most of them are actually under PI control. he practical advantages of PID controllers can be seen in a simple structure, in an understandable principle and in control capabilities. Moreover, PID controllers have survived changes in technology from pneumatic principles through analog and digital representation to DCS ones. It is widely known that PID controllers are quite resistant to changes in the controlled process without meaningful deterioration of the loop behavior. For 7 years, the Ziegler Nichols tuning rule has been glorified and vilified as well. Nevertheless, the Ziegler Nichols rule stay remains the most frequent method of PID tuning. However, there are many limitations, drawbacks and infirmities in the behavior of the Ziegler Nichols setting. A solution for qualified choice of controller parameters can be seen in more sophisticated, proper and automatic tuning of PID controllers. Manuscript received June 9, : Revised version received June,. his work was supported by the Ministry of Education, Youth and Sports of the Czech Republic under the Research Plan No. MSM 7885 and by the European Regional Development Fund under the project CEBIA- ech No. CZ..5./.. /.89. R. Prokop is with Faculty of applied informatics, omas Bata University in Zlín, Nad Stráněmi 45, Zlín, Czech Republic (phone: ; prokop@ fai.utb.cz). J. orbel is with Faculty of applied informatics, omas Bata University in Zlín, Nad Stráněmi 45, Zlín, Czech Republic ( korbel@fai.utb.cz). O. Líška is with Faculty of mechanical engineering, echnical University of ošice, Letná 9, ošice, Slovak Republic ( ondrej.liska@tuke.sk). he development of various autotuning principles was started by a simple symmetrical relay feedback experiment proposed by Åström and Hägglund in [] in the year 984. he ultimate gain and ultimate frequency are then used for adjusting of parameters by original Ziegler-Nichols rules. During the period of more than two decades, many studies have been reported to extend and improve autotuners principles; see e.g. [], [4], [8], [9]. he extension in relay utilization was performed in [], [5], [7], [4] by an asymmetry and hysteresis of a relay. Over time, the direct estimation of transfer function parameters instead of critical values began to appear. Experiments with asymmetrical and dead-zone relay feedback are reported in []. Also, various control design principles and rules can be investigated in mentioned s. Nowadays, almost all commercial industrial PID controllers provide the feature of autotuning. In this paper, a new combination for autotunig method of PI and PID controllers with an aperiodic control rule is proposed and developed. he basic autotuning principle combines an asymmetrical relay identification experiment and a control design performed in the ring of proper and stable rational functions R PS. he factorization approach proposed in [] was generalized to a wide spectrum of control problems in [], [], [5] - []. A different philosophy is reported in []. he pole placement problem in R PS ring is formulated through a Diophantine equation and the pole is analytically tuned according to aperiodic response of the closed loop. he proposed method is compared by an equalization setting proposed in []. A general basic scheme of the autotuning principle can be seen in Fig.. Naturally, there exist many principles of control design syntheses which can be used for autotuning principles, e.g. [], [], [], []. hey can be considered as alternative approach and only practical application test their abilities. II. RELAY FEEDBAC ESIMAION he estimation of the process or ultimate parameters is a crucial point in all autotuning principles. he relay feedback test can utilize various types of relay for the parameter estimation procedure. he classical relay feedback test [] was proposed for stable processes by symmetrical relay without hysteresis. Following sustained oscillation are then used for determining the critical (ultimate) values. he control parameters (PI or PID) are then generated in standard manner. Asymmetrical relays with or without hysteresis bring further progress [], [4]. After the relay feedback test, the estimation of process parameters can be performed. A typical data Issue 7, Volume 5, 8

2 response of such relay experiment is depicted in Fig.. he relay asymmetry is required for the process gain estimation () while a symmetrical relay would cause the zero division in the appropriate formula. In this paper, an asymmetrical relay with hysteresis is used. his relay enables to estimate transfer function parameters as well as a time delay term. For the purpose of the aperiodic tuning the time delay is not exploited. Fig. : Block diagram of an autotuning principle he model for first order (stable) systems plus dead time (FOPD) is supposed in the form: G( s) s + Θs and the process gain can be computed from (see []): iy iy y( t) dt ; i,,,.. PID w e u y Process _ Relay u( t) dt he time constant and time delay terms are given by []: y 6 u π ay y Θ π arctg arctg y ε ay ε where a y and y are depicted in Fig. and ε is the hysteresis. () () () Similarly, the second order model plus dead time (SOPD) is assumed in the form: G( s) ( s + ) Θs he gain is given by (), the time constant and time delay term can be estimated according to [] by the relation: 4 u y π a y y Θ π arctg arctg y ε ay ε III. ALGEBRAIC PI CONROL DESIGN he control design is based on the fractional approach; see e.g. [], [], [5] - [7]. Any transfer function G(s) of a (continuous-time) linear system is expressed as a ratio of two elements of R PS. he set R PS means the ring of (Hurwitz) stable and proper rational functions. raditional transfer functions as a ratio of two polynomials can be easily transformed into the fractional form simply by dividing, both the polynomial denominator and numerator by the same stable polynomial of the appropriate order. hen all transfer functions can be expressed by the ratio: b( s) n b( s) ( s + m) B( s) G( s) a( s) a( s) A( s) n ( s + m) n max(deg( a),deg( b)), m > (7) hen, all feedback stabilizing controllers for the feedback system depicted in Fig. are given by a general solution of the Diophantine equation: AP + BQ (8) (4) (5) (6) u(t) y(t) y which can be expressed with Z free in R PS : Q Q AZ P P + BZ (9) a y u In contrast of polynomial design, all controllers are proper and can be utilized. Fig. : Asymmetrical relay oscillation of stable process Fig. : Feedback (DOF) control loop Issue 7, Volume 5, 8

3 he Diophantine equation for designing the feedforward controller depicted in Fig. 4 is: F S + BR () w with parametric solution: R R Fw Z P P + BZ () where Z is free in the ring R PS. Asymptotic tracking is achieved by the choice: m Z (5) and the resulting PI controller is in the form: C( s) Q P q s + q (6) s where parameters q a q are given by: m m q q (7) he feedforward part of the DOF controller is from (): Fig. 4: FeedbackFeedforward (DOF) control loop Asymptotic tracking is then ensured by the divisibility of the denominator P in (9) by the denominator of the w G w / F w. he most frequent case is a stepwise with the denominator in the form: F w s ; m s + m > () he similar conclusion is valid also for the load disturbance d G d / F d. he load disturbance attenuation is then achieved by divisibility of P by F d. More precisely, for tracking and attenuation in the closed loop according to Fig. the multiple of AP must be divisible by the least common multiple of denominators of all input signals. he divisibility in R PS is defined through unstable zeros and it can achieved by a suitable choice of rational function Z in (9), see [], [5] for details. IV. PI AND PID-LIE CONROLLERS Diophantine equation (8) for the first order systems () without the time delay term can be easily transformed into polynomial equation: ( s + ) p + q s + m s + m with general solution: () s s r s + m s + m + with general solution: P + Z s + m m s R Z s + m he final PI controller is given: ( ) R r s + r C s P s (8) (9) () with parameters m + r m m r () he control synthesis for the SOPD is based on stabilizing Diophantine equation (8) applied for the transfer function (4) without a time delay term. he Diophantine equation (8) takes the form: ( ) ( s + m) ( s + m) s + ps + p qs + q + s + m s + m () P + Z s + m m s + Q Z s + m (4) and after equating the coefficients at like powers of s in () it is possible to obtain explicit formulas for p I, q i : Issue 7, Volume 5, 8

4 m p ; p q m ( m ) ; + q m ( m ) () he rational function P(s) has its parametric form (similar as in (4) for FOPD): P p s + p ( s + m) ( s + m) + Z (4) with Z free in R PS. Now, the function Z must be chosen so that P is divisible by the denominator of the which is pm (). he required divisibility is achieved by z. hen, the particular solution for P, Q is [ + ( + )] s p s p m p P ( s + m) q% s + q% s + q% Q ( s + m) where q% q + p m q% q + q m + p m q% q + p m., (5) (6) he final (asymptotic tracking) controller has the transfer function: Q q% s + q% s + q% C( s) P s( p s + ( p m + p )) (7) Also the feedforward part for the DOF structure can be derived for the second order system. For asymptotic tracking Diphantine equation takes the form: s ss + s + r s + m ( s + m) ( s + m) (8) he DOF control law is only dependent upon the rational function R wit general expression m s R Z (9) s + m Also with Z free in R PS. he final feedforward controller is: m ( s + m ) R C ( s) P s p s p m p [ + ( + )] () It is obvious that both parts of the controller (feedback and/or feedforward) depends on the tuning parameter m > in a nonlinear way. For both systems FOPD and SOPD the scalar parameter m> seems to be a suitable tuning knob influencing control behavior as well as robustness properties of the closed loop system. Naturally, both derived controllers correspond to classical PI and PID ones. It is clear that (6) represents the PI controller: u( t) P e( t) + e( τ ) dτ () I and the conversion of parameters is trivial. Relation () represents a PID in the standard four-parameter form []: u( t) P e( t) + e( ) d D y f ( t) τ τ + I τ y ( t) + y ( t) y ( t) f f V. APERIODIC UNING () Over the past 6 years after the introduction of Ziegler- Nichols rule in 94, vehement research activity in controller tuning has been performed. More than 4 tuning rules are referred in [], more than rules for PI controllers. A simple and attractive choice for the tuning parameter m> can be easily obtained analytically. In the R PS expression, the closed-loop transfer function wy is for () and PI controller (6) given in a very simple form: wy BQ (m ) s + m BQ AP + BQ ( s + m) () he step response of () can be expressed by Laplace transform: wy ks + k h( t) L L s s( s + m) L A B C, s ( s + m) ( s + m) + + (4) where A,B,C are calculated by comparing appropriate fractions in (4) and k m-, k m. he response h(t) in time domain is then mt mt h( t) A + Be + Cte (5) Issue 7, Volume 5, 8

5 he overshoot or undershoot of this response is characterized by the first derivative condition mt mt mt h ( t) mbe + C( e tme ) (6) From (6) time of the extreme of response h(t) is then easily calculated by the relation: C mb B te (7) mc m C VI. PROGRAM SYSEM IN MALAB For simple application of auto-tuning principle a program system was developed in Matlab-Simulink environment. his program enables an identification of the controlled system of arbitrary order as the first or second order transfer function with time delay. he user can choose if time delay should be neglected or approximated by Pade before control design. he program is developed with help of the Polynomial oolbox. Main menu of the program system can be seen in Fig. 5. Since the aperiodic response means that the extreme does not exist for positive t e, it implies t e < and after all substitutions of A,B,C, k, k relation (7) takes the simple form B < m C m (8) he denominator of (8) must be positive and less than and m> which implies the inequality: < m < (9) Any positive parameter m from (9) ensures aperiodic response. It is a question for further investigation and simulation what choice from interval (9) is the best. For autotuning philosophy time constant is always an estimation then the middle value of (9) would be reasonable, it means the choice m 4 (4) Also other tuning principles for aperiodic tuning certainly exist. For the mentioned algebraic synthesis, the equalization method developed by Gorez and lán in []. he idea goes out from PI controller in the form (7). he tuning rule is very simple and it leads in relations:.4 (4) P I u where is a process gain and u is the ultimate period obtained from the Ziegler-Nichols experiment. However, the fulfillment of (4) by unique value of m> is impossible, see [6]. he exact fulfillment of both relations in (4) could be obtained in the case of two distinct roots in denominator (), so (s+m )(s+m ) instead of (s+m). Fig. 5: Main Menu Firstly, the controlled transfer function is defined and parameters for the relay experiment can be adjusted. hen, the experiment is performed and it can be repeated with modified parameters if necessary. After the experiment, an estimated transfer function in the form () is performed automatically and controller parameters are generated after pushing of the appropriate button. Parameters for experimental adjustment are defined in the upper part of the window. he second phase of the program routine is a control design. According to above mentioned methodology, the controller in standard scheme (see Fig. ) is derived and displayed. hen the simulation routine a standard Simulink scheme is performed and required outputs are displayed. he simulation horizon can be prescribed as well as tuning parameter m, other simulation parameters can be specified in the Simulink environment. In all simulation a change of the step is performed in the second third of the simulation horizon and a step change in the load is injected in the last third. A typical control loop in Simulink is depicted in Fig. 6. Fig. 6: Control loop in Simulink Issue 7, Volume 5, 84

6 VII. EXAMPLES AND ANALYSIS he following examples illustrate the situation where the estimated model is always of the first order ones () without time delay and the controller has a PI structure (6). Example : he first order system governed by the transfer function G(s) was after the relay experiment estimated by G% ( s) in the form: G( s) G% ( s) (4) s +.7s + he PI controller was then generated for three values of m within the interval given by (9), m.85;.78;.7, respectively. he responses are depicted in Fig his choice represents the lowest, middle and upper limit values in derived interval (9). Responses in Fig. 8 demonstrate that all ones have aperiodic behavior. Example : A second order (stable) system G(s) without a time delay was estimated by a first order model in the above mentioned relay experiment. Both transfer functions have the form:. G( s) G( s) (s + ).89s + %.5s (4) he above mentioned relay experiments enable to estimate the original system by the first or second order transfer functions (), (4). Step responses without time delay terms are depicted in Fig. 9. he PI controller generated from the ~ approximated system G ( s ) was designed by (), (4) for three values of tuning parameters m> with respect the interval given by (9). he responses are shown in Fig Approx. system ime (sec) Fig. 7: Step responses of systems (4) Approx. system w /o transport delay Approx. system w ith transport delay ime (sec) Fig. 9: Step responses of systems (4).5.5 m.85 m.78 m ime (s) Fig. 8: Control responses (Example ) m.9 m.9 m ime (s) Fig. : Control responses (Example ) Issue 7, Volume 5, 85

7 Second order identification of example :. G( s) G% ( s) (44) (s + ).89s +.95s +.5 controlled and estimated systems is considerable, it can be expected that not all values of and some of m> represent acceptable behavior. With respect of (9), three responses are shown in Fig. 4. Generally, larger values of m> implicate larger overshoots and oscillations. As a consequence, for inaccurate relay identifications, lower values of m> in interval (9) can be recommended Approx. system w /o transport delay ime (sec).5 Fig. : Step responses of systems (44).5 Approx. system w /o transport delay Approx. system w ith transport delay ime (sec) Fig. : Step responses of systems (45).5.5 m. m.4 m ime (s) Fig. : Control responses (Example ) Example : A higher order system (8 th order) with transfer function G(s) is supposed. Again, after the relay experiment, a ~ first order estimation G ( s ) was identified, both governed by: G( s) G( s) 8 ( s + ).5s + % 5.s (45) he step responses of systems (45) are shown in Fig.. Naturally, the step response of the estimated system is quite different from the nominal system G(s). Again, PI controllers are generated from (), (4) and the tuning parameter m> can influence the control responses. Since the difference of In all control simulations, the value is changed in / of the simulation horizon and the load disturbance is injected in the / of the simulation horizon. All simulations were performed in Simulink environment. In the case of (45), the best response is achieved for m m.4 m. m ime (s) Fig. 4: Control responses (Example ) Second order identification of example : G( s) G( s) ( s + ) 4.86s + 4.4s + % 4s (46) 8 Issue 7, Volume 5, 86

8 .5.5 ACNOWLEDGMEN his work was supported by the Ministry of Education, Youth and Sports of the Czech Republic under the Research Plan No. MSM 7885 and by the European Regional Development Fund under the project CEBIA-ech No. CZ..5./.. / Approx. system w ith transport delay ime (sec) Approx. system w /o transport delay Fig. 5: Step responses of systems (46) m. m.45 m ime (s) Fig. 6: Control responses (Example ) VIII. CONCLUSION his contribution gives a new combination of relay feedback identification and a control design method. he estimation of a low order transfer function parameters is performed from asymmetric limit cycle data. he control synthesis is carried out through the solution of a linear Diophantine equation according to [], [5], [6]. his approach brings a scalar tuning parameter which can be adjusted by various strategies. A first order estimated model generates PI-like controllers while a second order model generates a class of PID ones. he aperiodic tuning through the parameter m> is proposed by the analytic derivation. he methodology is illustrated by several examples of various orders and dynamics. REFERENCES [] Ch.Ch. Yu, Autotuning of PID Controllers. Springer, London, 999. [].J. Åström and. Hägglund, Automatic tuning of simple regulators with specification on phase and amplitude margins. Automatica, Vol., 984, pp [].J. Åström and. Hägglund, PID Controllers: heory, Design and uning. Research riangle Park, NC: Instrumental Society of America, 995. [4] R.F. Garcia and F.J.P. Castelo, A complement to autotuning methods on PID controllers, Iin: Preprints of IFAC Workshop PID, pp. -4,. [5] R.R. Pecharromán and F.L. Pagola, Control design for PID controllers auto-tuning based on improved identification, In: Preprints of IFAC Workshop PID, pp ,. [6] C.C.Hang,.J. Åström and Q.C. Wang, Relay feedback auto-tuning of process controllers a tutorial review, Journal of Process Control, Vol., No6,. [7]. hyagarajan and Ch.Ch. Yu, Improved autotuning using shape factor from relay feedback, In: Preprints of IFAC World Congres,. [8] S. Majhi and D.P. Atherton, Autotuning and controller design for unstable time delay processes, In: Preprints of UACC Conf an Control, 998, pp [9] F. Morilla, A. Gonzáles and N. Duro, Auto-tuning PID controllers in terms of relative damping, In: Preprints of IFAC Workshop PID,, pp [] M. Vítečková and A. Víteček Experimentální identifikace metodou relé (in Czech), In: Automatizácia a informatizáci, 4. [] M. Vidyasagar, Control system synthesis: a factorization approach. MI Press, Cambridge, M.A. (987). [] V. učera, Diophantine equations in control - A survey, Automatica, Vol. 9, No. 6, 99, pp [] R. Gorez and P. lán, Nonmodel-based explicit design relations for PID controllers, In: Preprints of IFAC Workshop PID,, pp [4] I. aya and D.P. Atherton, Parameter estimation from relay autotuning with asymmetric limit cycle data, Journal of Process Control, Vol., No4,, pp [5] R. Prokop and J.P. Corriou, Design and analysis of simple robust controllers, Int. J. Control, Vol. 66, 997, pp [6] R. Prokop, J. orbel and Z. Prokopová, Relay feedback autotuning A polynomial approach, In: Preprints of 5th IFAC World Congress,. [7] R. Prokop, orbel, J., Prokopová, Z., Relay based autotuning with algebraic control design, In: Preprints of the rd European Conf. on modelling and Simulation, Madrid, 9, s [8] R Matušů and R. Prokop, Robust Stabilization of Interval Plants using ronecker Summation Method. In: Last rends on Systems, 4th WSEAS International Conference on Systems, Corfu Island, Greece,, pp [9] L. Pekař and R. Prokop, Non-delay depending stability of a time-delay system. In: Last rends on Systems, 4th WSEAS International Conference on Systems, Corfu Island, Greece,, pp [] L. Pekař and R. Prokop, Control of Delayed Integrating Processes Using wo Feedback Controllers: RMS Approach, In: Proceedings of the 7th WSEAS International Conference on System Science and Simulation in Engineering, Venice, 8, pp [] D. rokavec and A. Filasová, Pole assignment in robust state observer design. In: A&P Journal Plu,. Vol., č. (7), s [] A. O Dwyer, Handbook of PI and PID controller tuning rules. London:Imperial College Press,. [] L. Pekař, & R. Prokop: Algebraic Control of integrating Processes with Dead ime by wo Feedback Controllers in the Ring RMS. Int. J. of Issue 7, Volume 5, 87

9 Circuits, Systems and Signal Processing, Volume, Issue 4, 8, pp ISSN: [4] P. Dostálek, J. Dolinay, V. Vašek & L. Pekař. Self-tuning digital PID controller implemented on bit Freescale microcontroller. International Journal of Mathematical Models and Methods in Applied Sciences, Volume 4, Issue 4,, pp ISSN: [5] L. Pekař, R. Prokop & R. Matušů. Stability conditions for a retarded quasipolynomial and their applications. International Journal of Mathematics and Computers in Simulations, Volume 4, Issue,, pp ISSN: [6] R. Matušů & R. Prokop. Experimental verification of design methods for conventional PI/PID controllers. WSEAS rans. on Systems and Control, Vol. 5, Issue 5,, pp [7] R. Matušů & R. Prokop. Control of systems with time-varying delay: A comparison study. th WSEAS International Conference on Automatic Control, Modelling and Simulation, ACMOS ',, pp. 5-. ROMAN PROOP was born in Hodonin, Czech Republic in 95. He graduated in Cybernetics from the Czech echnical University in Prague in 976. He received post graduate diploma in 98 from the Slovak echnical University. Since 995 he has been at omas Bata University in Zlín, where he presently holds the position of full professor of the Department of Automation and Control Engineering and a vice-rector of the university. His research activities include algebraic methods in control theory, robust and adaptive control, autotuning and optimization techniques. His address is: prokop@fai.utb.cz. JIŘÍ ORBEL was born in Zlín, Czech Republic. He studied automatic control and informatics at the omas Bata University and graduated in 4, now he is an post-graduate student and assistant at the Faculty of Applied Informatics in Zlín. His research activities include autotuning principles, algebraic and polynomial syntheses and modeling and simulations. His address is: korbel@fai.utb.cz. ONDREJ LÍŠA was born in ošice, Slovak Republic. He graduated from echnical University in ošice in 977. Doctor s degree he has received in 985 from the same university. He is working in echnical University in ošice, Faculty of Mechanical engineering, Department Automation and Control. He is now working there as an associating professor. His research activities: control theory, automation a control of machines and processes. His address is: ondrej.liska@tuke.sk. Issue 7, Volume 5, 88