Filter-Generating Systems
|
|
- Annice Allen
- 6 years ago
- Views:
Transcription
1 24 IEEE TRANSACTIONS ON CIRCUITS AND SYSTEMS II: ANALOG AND DIGITAL SIGNAL PROCESSING, VOL. 47, NO. 3, MARCH 2000 Filter-Generating Systems Saed Samadi, Akinori Nishihara, and Hiroshi Iwakura Abstract Combining the methods of generating functions and discrete-time linear systems, we can develop multidimensional (M-D) digital systems for systematic generation of entire families of interrelated digital filters. These M-D systems, dubbed filter-generating systems, are mostly of infinite-impulse response (IIR) type and can produce the impulse response sequence of any member of the family. Temporal and spatio-temporal implementation of filter-generating systems are studied. A temporal implementation scheme is devised for causal filter-generating systems in order to implement an arbitrary filter member using (M-D) signal processing techniques. It is shown that this may result in low order recursive filtering structures that can implement arbitrarily high order members of the family. A spatio-temporal implementation scheme is developed for generation of regular signal flow-graphs for the generated family of finite-impulse response (FIR) filters. It is shown that the signal flow-graphs give rise to cellular array structures. Concrete eamples are provided for maimally flat FIR filters. Inde Terms Cellular array structures, digital filters, generating function, maimally flat magnitude response, systolic arrays, z transform. I. INTRODUCTION We develop a novel technique for generation and implementation of families of digital filters using multidimensional (M-D) systems that we call filter-generating systems. The technique utilizes the recursive relationship eisting in some classes of finite-impulse response (FIR) digital filters. It is shown that for some families of FIR digital filters, it is possible to derive infinite-impulse response (IIR) filter-generating systems of low orders that generate the whole class of the filters as their impulse-response sequence. The filter-generating system may then be used to generate any desired filter of the family, with arbitrarily high order, provided that sufficient processing time and computational resources are available. Filter-generating systems can be used for three purposes. First, they can be used as an algebraic or analytic apparatus for generation of the impulse response coefficients of the family, or designing new families of FIR filters. Alternatively, they can be used as an implementation tool to provide efficient filtering algorithms for the family. If used in such fashion, filter-generating systems can operate as variable-length filters that can produce output sequences corresponding to any desired filter in the family. As a useful by-product, in the process of generating the intended output sequence, they successively generate output sequences that are results of filtering the input signal by lower order filters of the family. The processing speed of such implementations is mainly constrained by the order of the desired filter and the order of the filter-generating system. Third, we will see that filter-generating systems are very efficient tools for systematic generation of various modular structures for the associated family of filters. These are array structures consisting of layers of identical building blocks that are interconnected in a series-parallel configuration and are suitable for high-speed systolic implementations. Filter-generating systems provide a mathematical tool for design and manipulation of such array structures. Manuscript received April 999; revised October 999. This paper was recommended by Associate Editor M. Simaan. S. Samadi and H. Iwakura are with the Department of Information and Communication Engineering, the University of Electro-Communications, Tokoyo, Japan. A. Nishihara is with the Center for Research and Development of Educational Technology, Tokyo Institute of Technology, Tokyo, Japan. Publisher Item Identifier S (00) The concept of filter-generating systems is a hybrid of the z transform [] and the method of generating functions [2], two closely related tools used in computer science, engineering, and mathematics. An early application of generating functions to digital filter design can be found in [3]. Hamming describes a method based on manipulation of a generating function for Bessel functions to design discrete-time integrators. A recent work by Schmidlin [4] may be regarded as an eample of the largely uneplored possibilities of combining the concepts of generating functions and z transforms. Our main focus here is on the application of generating function framework to implementation and modular realization of families of FIR digital filters. If the z transform polynomials corresponding to the transfer functions of a family of digital filters, or any discrete-time linear shift-invariant (LSI) system, can be put in this framework, and generating functions with rational closed forms can be derived as the result. Then, we get a multivariable function that can be viewed as the transfer function of a higher dimensional LSI system. This system is a filter-generating system. As a concrete eample, we show that at least one well-known family of FIR digital filters, the linear-phase maimally flat FIR filters, possesses very simple rational filter-generating functions. We use this function to derive array structures for modular realization of the member filters. II. FILTER-GENERATING FUNCTIONS AND SYSTEMS Consider the rational function P A i (z) i G(; z)= i=0 0 P B i(z) i () i= where A i (z) and B i (z) are polynomials in indeterminate z 0. Epanding G(; z) as a power series in ; we have G(; z)= H i(z) i (2) i=0 where H i (z) are polynomials composed of A i (z) and B i (z). The polynomials H i (z) can be viewed as transfer functions of FIR discrete-time systems. The degree of H i(z) tends to increase with the inde i,however this is not a general rule. Now consider a family of digital systems fh i (z); i =0; ; g. The family may contain a finite or infinite number of digital filters. For eample, we can think of a family of filters with increasing orders that give improved approimations to an ideal frequency response as the inde i increases. We define the formal power series G(; z) of the form (2) as the filter-generating function for the family. Note that the convergence of the defined power series is not of our concern here as is the case for other formal power series [5]. Now, if a closed-form rational epression of the form () eists for the defined generating function, then it is possible to view the polynomials A i(z) and B i(z) as the coefficients of a one-dimensional (-D) discrete-time LSI system with delay operator. This system is called the filter-generating system for the family and operates on polynomial signals in indeterminate z 0. The filter-generating system may be an FIR or IIR system, depending on the actual forms of the coefficients A i (z) and B i (z). If the filter-generating system is ecited by a polynomial impulse signal under the condition of zero initial states, the ith impulse response of the system is a polynomial equal to H i (z), i.e., /00$ IEEE
2 IEEE TRANSACTIONS ON CIRCUITS AND SYSTEMS II: ANALOG AND DIGITAL SIGNAL PROCESSING, VOL. 47, NO. 3, MARCH Fig.. Direct-form recursive structure for rational filter-generating system. Transfer functions of the associated family of FIR filters appear as the impulse-response sequence. g(n )j n =i = H i (z), where g(n ) denotes the n th (n =0; ; ) impulse response coefficient of the -D system (with respect to ) G(; z). In this way, we can generate the transfer functions of the entire members of the family fh i (z)g. In the above argument, G(; z) is considered as a -D function in whose coefficients are polynomials in z 0. If the generated family of FIR filters contains an infinite number of elements, the associated filter-generating system should be an IIR system, i.e., there should eist at least one B i(z) 6=0. Using a well-known recursive structure for realization of IIR systems, the filter-generating system can be realized as a special recursive -D system as shown in Fig.. The system of Fig. operates on polynomial signals by performing polynomial additions, polynomial multiplications and polynomial delays. As mentioned above, the system can be used to compute the transfer functions of the filters H i (z) in a successive manner by applying the polynomial impulse sequence (n )= ; n =0 0; n =; 2; which is identical to the numerical discrete-time impulse sequence, and then taking the output polynomial signal at the ith sample. If the members of a family of digital filters are doubly indeed as H i; j (z), the definition of filter-generating function can be etended as G(; y; z)= H i; j (z) i y j : (3) with polynomial coefficients A i; j(z) and B i; j(z) is called the filtergenerating system of the family. Like the -D case, the transfer functions of the members H i; j (z) can be computed by applying a 2-D polynomial impulse signal of the form (n ;n y )= ; n = n y =0 0; n ;n y =; 2; and taking the output at the appropriate instance. The discrete variables n and n y correspond to indeterminates and y of the generating function, respectively. The application of the filter-generating system is not limited to the computation of transfer functions. Net, we devise a method to use the system as a filtering structure that can process conventional numerical signals. III. TEMPORAL IMPLEMENTATION OF FILTER GENERATING SYSTEMS Let u(n z ) be the -D input signal we wish to convolve with the ith member of the family fh i(z)g. The result of convolution is denoted by u 3 h i. The discrete-time variable n z takes on nonnegative integer values. The use of suffi z emphasizes the correspondence of the variable to the summation counter in the z transform of the input signal. In the preceding section, we made a similar usage of the suffies and y in n and n y, respectively. Those suffies correspond to the location of the member filters in the filter-generating system. Henceforth, we will use the three suffies, y, and z to distinguish between the discrete variables. Now consider the 2-D impulse response sequence g(n ;n z) of the filter-generating function G(; z) () that is now looked upon as a 2-D system. The impulse response coefficients of the filter H i (z) appear at the ith row of the 2-D impulse response, i.e., Again if a closed-form rational epression can be obtained for the above formal power series, the two-dimensional (2-D) LSI system (in and y) P Q A i; j (z) i y j G(; y; z)= (4) P Q 0 B i; j(z) i y j g(n ;n z )j n =i = h i (n z ) (5) where h i(n z) denotes the n zth impulse response coefficient of the ith filter of the family, i.e., H i (z)= n =0 h i(n z )z 0n. In other words, the filter-generating system can be viewed as a 2-D causal IIR system that, when ecited by the 2-D impulse signal, generates the impulse response of the ith member of the family at the ith row of its 2-D impulse response. Now we convert the input signal u(n z ) to the 2-D signal u(n ;n z)= u(n z); n =0 0; otherwise (6)
3 26 IEEE TRANSACTIONS ON CIRCUITS AND SYSTEMS II: ANALOG AND DIGITAL SIGNAL PROCESSING, VOL. 47, NO. 3, MARCH 2000 Fig. 2. Filtering an infinite length -D signal using 2-D IIR filter-generating system; a temporal scheme. and feed it to the filter-generating system. We get a 2-D output sequence of the form v(n ;n z )= u(i; j)g(n 0 i; n z 0 j): (7) Using (5) and (6) we can rewrite this as 0 v(n ;n z )= u(0; j)g(n ;n z 0 j) = u(j)h n (n z 0 j) =u 3 h n : (8) j=0 The above relations show that the filter-generating system G(; z) can be used to convolve the -D signal u(n z ) and the sequence h i (n z ), the impulse response of the ith member of the family of generated FIR filters, using the simple scheme illustrated in Fig. 2. In the above description, we considered a 2-D filter-generating system implemented as a recursive IIR system. A main concern with IIR systems is the stability of the system, which is an asymptotic concept. However, stability issues do not arise in the temporal implementation of the filter-generating system, for the subject of operation undergoes, in effect, FIR filtering in one direction (z direction), and for the other direction ( direction), the operation is terminated after a finite number of iterations. Temporal implementation of filtering structures using 3-D generating systems follows from the 3-D etension of the method proposed for the 2-D case. IV. SPATIO-TEMPORAL IMPLEMENTATION OF FILTER-GENERATING SYSTEMS Another method for filtering digital signals through the filter-generating system is a spatio-temporal scheme that generates modular array structures for the family of filters. In this scheme, the indeterminate z 0 is regarded as a delay operator in time while is regarded as a spatial delay operator, a delay operator that acts on the nodes of system s signal flow-graph. We consider three types of rational filter-generating systems G(; z), namely: ) nonrecursive; 2) all-pole; and 3) general recursive filter-generating systems. We provide a simple and systematic method for deriving modular array structures for members of the family generated by G(; z). A. Nonrecursive Filter-Generating Systems Consider the second order filter-generating system G(; z) =A0(z) +A(z) + A2(z) 2 : (9) This system can be associated with the -D difference equation v(n )= A0(z)u(n )+A(z)u(n 0 ) + A2(z)u(n 0 2) n =0; ; (0) where v(n ) and u(n ) denote the spatial (as opposed to temporal) input and output signals, respectively. These signals can also be associated with the nodes of a signal flow-graph. Hence, eecution of the recurrence under the assumption of zero initial values can be performed over a signal flow-graph as shown in Fig. 3(a). Higher order generating systems can be built in a similar manner. The number of branches incident to each computing node increases with the order of the generating system. If only local connections are desired, the order of the generating system should be at most in. Plugging the spatial impulse signal (n ) into the above recurrence is equivalent to allocating values or 0 to the source nodes of the signal flow-graph. We then get the transfer functions fh i (z); i=0; ; g of the associated family of digital filters as the impulse response at sink nodes. Thus, the signal flow-graph gives rise to a modular structure for realization of the digital filters in the family. Evidently, there are only three non-zero transfer functions in the family generated by the second order generating system, namely, H i (z) =A i (z), i =0; ; 2. Later, we will give eamples where nonrecursive generating systems appear in cascade with all-pole generating systems. B. All-Pole Filter-Generating Systems For the second order all-pole filter-generating system G(; z) = we get a spatial difference equation of the form 0 B(z) 0 B2(z) 2 () v(n )= u(n )+B(z)v(n 0 ) + B2(z)v(n 0 2); n =0; ; (2) which, under zero initial conditions, gives rise to the signal flow-graph of Fig. 3(b). Again to restrict the connections to a local form, the generating system should be of order at most in. When driven with the impulse sequence, the signal flow-graph generates digital filters H i (z), i =0; ;. An infinite number of filters can be generated due to the recursive form of generating function. However, in practice, the signal flow-graph is terminated at the sink node associated with the desired member of the family. The modularity of the resulting filter structure is evident.
4 IEEE TRANSACTIONS ON CIRCUITS AND SYSTEMS II: ANALOG AND DIGITAL SIGNAL PROCESSING, VOL. 47, NO. 3, MARCH (a) (b) (c) Fig. 3. Spatio-temporal implementation of: (a) nonrecursive; (b) all-pole; and (c) general recursive generating systems of order 2. Applying the -D impulse signal u(n )= (n ), the members of the family will be generated at sink nodes v(n ). C. General Recursive Filter-Generating Systems A general rational generating system G(; z) can be decomposed to the cascade of an FIR system G (; z) and an all-pole IIR system G 2 (; z). For a second-order system, we have G (; z) =A 0(z) +A (z) + A 2(z) 2 G 2(; z) = B 0 (z) 0 B (z) 0 B 2 (z) 2 : (3) Since the scope of this brief is limited to generation of FIR filters, we are concerned with the special case of B 0 (z) =. We can write the spatial difference equations for the cascaded structure as v (n )=A0(z)u(n )+A(z)u(n 0 ) + A2(z)u(n 0 2) v 2 (n )=v (n )+B (z)v 2 (n 0 ) + B 2 (z)v 2 (n 0 2); n =0; ; : (4) The recurrence can be carried out by the signal flow-graph shown in Fig. 3(c). Recall that for the impulse input signal, the output sequence v (n ) takes on zero values for n 3. Therefore, we need to carry out the eecution of the associated recurrence only for n =0; ; 2. On the other hand, the system G 2 (; z) is an all-pole IIR system and the difference equation produces an infinite-length sequence of nonzero output values. We need to carry out the recurrence up to n = i to realize the filter H i (z). This means that for the spatial impulse signal, the upper layer of the signal flow-graph may be simplified to three nodes while the lower layer needs all i nodes. The simplified signal flow-graph is given in Fig. 4(a). The overall modular filter structure generated by the system is illustrated in Fig. 4(b). It consists of a conditioning part for the first 3 modules, generated by the numerator of the generating function, and a modular part generated due to the recursive structure of the generating system. The generated -D filter is implemented by feeding the input signal from the source node that is labeled with a in Fig. 4(a). The source nodes labeled with a 0 are fed with the zero sequence. The output taken at the ith port is the signal filtered by H i (z). In general, if the generating system G(; z) can be decomposed to the cascade of K subsystems, the resulting family of filters can be real-
5 28 IEEE TRANSACTIONS ON CIRCUITS AND SYSTEMS II: ANALOG AND DIGITAL SIGNAL PROCESSING, VOL. 47, NO. 3, MARCH 2000 (a) (b) Fig. 4. Spatio-temporal implementation of a recursive filter-generating system of order 2. The scheme results in a modular array for the desired filter that simultaneously generates all filters of lower orders. (a) Overall signal flow-graph driven by the impulse sequence, after simplification. (b) Modular filter structure. ized by interconnecting the corresponding sink and source nodes of the signal flow-graphs generated by subsystem difference equations. This is shown schematically in Fig. 5, where a layered signal-flow graph is formed. The impulse sequence is applied at the source nodes of the first subsystem and all initial conditions are set to zero. Since the degree of each subsystem depends on the actual forms of the overall coefficient polynomials A i(z) and Bi(z), the number of interlayer (horizontal) and intralayer (vertical) interconnections is not specified. The branch transmittances are not shown either. V. FILTER-GENERATING SYSTEMS FOR MAXIMALLY FLAT FIR FILTERS A. Basic Formulas In this section, we provide a concrete eample of a family of filters with a simple rational generating function. We give details of temporal and spatio-temporal implementations of the family using its filter-generating system. The maimally flat linear-phase FIR filters construct a family of digital filters whose members are denoted by H i; j (z). The suffies i and j represent the degrees of flatness of the 2(i + j 0 )th order maimally flat filter H i; j (z) at frequencies! =0and! =, respectively. Specifically, the zero-phase response of the filters has 2i 0 vanishing derivatives at! = 0and 2j 0 vanishing derivatives at! =. A number of eplicit epressions have been derived in the literature for H i; j(z). In [7] it is shown that using the Bernstein approimation, the transfer function of low-pass maimally flat filters can be written as H i; j(z) = i0 p=0 i + j 0 p (Q(z)) p (P (z)) i+j00p (5) where the two kernel filters P (z) and Q(z) are given as P (z) = +z0 2 2 ; Q(z) =0 0 z0 2 2 : (6)
6 IEEE TRANSACTIONS ON CIRCUITS AND SYSTEMS II: ANALOG AND DIGITAL SIGNAL PROCESSING, VOL. 47, NO. 3, MARCH Fig. 5. General connection patterns in signal flow-graphs generated by spatio-temporal implementation of the cascade of K filter-generating systems. (a) (b) Fig. 6. (a) Filter-generating system for maimally flat FIR filters. (b) Using the 3-D etended scheme of Section III, the system can be used to implement any desired FIR maimally flat filter. This formula was initially derived in [6] via a different method. The Bernstein representation of the transfer function leads to a recursive decomposition of H i; j (z) in terms of filters of lower orders. The recursive representation and initial conditions are given as H i; 0(z) =z 0(i0) ; i =; 2; H 0;j (z) =0; j =0; ; H i; j (z) =P (z)h i; j0(z) +Q(z)H i0;j(z); i; j : (7) B. Filter-Generating System for Entire Family The generating function for fh i; j (z); i 0; j 0g defined by (5) can be written as G(; y; z) = H i; j (z) i y j : (8) Using the relations given in (7), we have G(; y; z) = = i= z 0(i0) i + 0 z0 + y i= j= H i; j(z) i y j (P (z)h i+; j(z) + Q(z)H i; j+(z)) i y j : (9) The right-hand side of the last relation above can be epressed as G(; y; z) = 0 z0 + yp (z)g(; y; z) +Q(z) G(; y; z) 0 0 z0 : (20)
7 220 IEEE TRANSACTIONS ON CIRCUITS AND SYSTEMS II: ANALOG AND DIGITAL SIGNAL PROCESSING, VOL. 47, NO. 3, MARCH 2000 (a) (b) Fig. 7. Array realization of maimally flat FIR filters using filter-generating system. (a) Signal flow-graph. (b) Simplified signal flow-graph. Solving (20) for G(; y; z) we have G(; y; z)= ( 0 Q(z)) ( 0 z 0 )( 0 Q(z) 0 P(z)y) : (2) This is an eplicit formula for filter-generating function of the entire family of linear-phase maimally flat filters fh i; j (z)g. Note that the filter-generating function may take other forms depending on the way we number the filters. Thus, (2) serves as the generating function for the filters numbered according to our convention. Fig. 6 shows a recursive temporal structure for the three-dimensional (3-D) transfer function G(; y; z) and a method for implementing the generated -D FIR filters. This method is a straightforward 3-D etension of the scheme developed in Section III for temporal implementation of 2-D filter-generating systems. Note that the recursive computation is terminated after a prespecified number of iterations in and y directions while for the z direction it continues as long as input samples are fed to the system. It is intriguing that the whole family of maimally flat filters can be implemented via a simple recursive LSI structure of order 2 that requires no multiplier coefficients ecept simple powers of /2.
8 IEEE TRANSACTIONS ON CIRCUITS AND SYSTEMS II: ANALOG AND DIGITAL SIGNAL PROCESSING, VOL. 47, NO. 3, MARCH (c) Fig. 7. (Continued.) Array realization of maimally flat FIR filters using filter-generating system. (c) Cellular mesh array structure. Net, let us consider the spatio-temporal implementation of the system (2). The system can be decomposed as G(; y; z) =G (; z)g 2(; z)g 3(; y; z), where G (; z) = 0 z 0 G 2(; z) =0 Q(z) G 3(; y; z) = 0 Q(z) 0 P (z)y : (22) For the overall cascaded system, we can write difference equations of the forms v (n )=u(n 0 ) + z 0 v (n 0 ) v 2 (n )=v (n ) 0 Q(z)v (n 0 ) v 3(n ;n y)=v 2(n ;n y)+q(z)v 3(n 0 ; n y) where + P (z)v 3 (n ;n y 0 ); n ;n y =0; ; v 2(n ;n y)= v2(n); ny =0 0; n y =; 2;. (23) (24) Implementation of the above recurrences over a signal flow-graph for the -D impulse input signal u (n )=(n ) is illustrated in Fig. 7(a). It can be seen that many nodes and branches of the first and second recurrences contribute to redundant computations and hence can be removed. The simplified signal flow-graph is given in Fig. 7(b). Finally, a modular structure for the nontrivial filters in the family is given in Fig. 7(c). VI. CONCLUSION Filter-generating systems contain, in a very compact form, all information needed to synthesize and implement an entire family of digital systems using the most basic properties underlying each member of the family. They can be thought of as a compressed form of the transfer functions of the members of the family that may be unfolded to yield any member of the family whenever necessary. An equivalently important point of view emerges from the possibility of implementing any filter member of the family, of arbitrarily high order, using low-order M-D recursive filter-generating structures. Filter-generating systems also provide a systematic method to develop arrays of regularly interconnected signal flow-graph nodes with simple and in some cases almost identical branch transmittances for the members of the family. This gives rise to a cellular realization of the filter members through regularly interconnected identical cells of low orders. Such cellular structures are interesting from both theoretical and practical considerations. They may yield high-speed systolic architectures suitable for VLSI digital circuits that inherit the desirable property of scalability. Note that there is a connection between the overall dimension M (including z) of the generating system and that of the array realization of the family. An M -dimensional generating system for a family of -D filters has an M 0 -dimensional array realization. For eample, a 3-D generating system has a 2-D mesh array realization as shown in Section V. The application of the proposed techniques need not be limited to frequency-selective maimally flat systems; any family of LSI discrete-time systems with recursive relation between the members of the family may be a suitable candidate. If the concept of filter-generating systems is to be used for designing new families of digital filters, we need a method to connect the properties of the M-D generating system with those of the family of generated digital filters. For instance, to design novel families of maimally flat filters, we should look for a 2-D or 3-D property that corresponds to the -D maimal flatness of the resulted family. This issue will be addressed in a future work. REFERENCES [] E. I. Jury, Theory and Application of the Z-Transform Method. Huntington, NY: R. E. Krieger, 973. [2] H. S. Wilf, Generatingfunctionology, 2nd ed. San Diego, CA: Academic, 994. [3] R. W. Hamming, Digital Filters. Englewood Cliffs, NJ: Prentice-Hall, 977. [4] D. J. Schmidlin, Realization of irrational transfer functions, IEEE Trans. Circuits Syst. I, vol. 43, pp , July 996. [5] R. L. Graham, D. E. Knuth, and O. Patashnik, Concrete Mathematics. Reading, MA: Addison-Wesley, 989. [6] J. A. Miller, Maimally flat nonrecursive digital filters, Electron. Lett., vol. 8, pp , 972. [7] L. R. Rajagopal and S. C. Dutta Roy, Design of maimally-flat FIR filters using the Bernstein polynomial, IEEE Trans. Circuits Syst., vol. CAS-34, pp , Dec. 987.
Maximally Flat Lowpass Digital Differentiators
Maximally Flat Lowpass Digital Differentiators Ivan W. Selesnick August 3, 00 Electrical Engineering, Polytechnic University 6 Metrotech Center, Brooklyn, NY 0 selesi@taco.poly.edu tel: 78 60-36 fax: 78
More informationClosed-Form Design of Maximally Flat IIR Half-Band Filters
IEEE TRANSACTIONS ON CIRCUITS AND SYSTEMS II: ANALOG AND DIGITAL SIGNAL PROCESSING, VOL. 49, NO. 6, JUNE 2002 409 Closed-Form Design of Maximally Flat IIR Half-B Filters Xi Zhang, Senior Member, IEEE,
More informationLecture 19 IIR Filters
Lecture 19 IIR Filters Fundamentals of Digital Signal Processing Spring, 2012 Wei-Ta Chu 2012/5/10 1 General IIR Difference Equation IIR system: infinite-impulse response system The most general class
More informationLecture 11 FIR Filters
Lecture 11 FIR Filters Fundamentals of Digital Signal Processing Spring, 2012 Wei-Ta Chu 2012/4/12 1 The Unit Impulse Sequence Any sequence can be represented in this way. The equation is true if k ranges
More informationDesign of Orthonormal Wavelet Filter Banks Using the Remez Exchange Algorithm
Electronics and Communications in Japan, Part 3, Vol. 81, No. 6, 1998 Translated from Denshi Joho Tsushin Gakkai Ronbunshi, Vol. J80-A, No. 9, September 1997, pp. 1396 1402 Design of Orthonormal Wavelet
More informationHow to manipulate Frequencies in Discrete-time Domain? Two Main Approaches
How to manipulate Frequencies in Discrete-time Domain? Two Main Approaches Difference Equations (an LTI system) x[n]: input, y[n]: output That is, building a system that maes use of the current and previous
More informationImplementation of Discrete-Time Systems
EEE443 Digital Signal Processing Implementation of Discrete-Time Systems Dr. Shahrel A. Suandi PPKEE, Engineering Campus, USM Introduction A linear-time invariant system (LTI) is described by linear constant
More informationAdaptive Inverse Control
TA1-8:30 Adaptive nverse Control Bernard Widrow Michel Bilello Stanford University Department of Electrical Engineering, Stanford, CA 94305-4055 Abstract A plant can track an input command signal if it
More informationDiscrete-Time Systems
FIR Filters With this chapter we turn to systems as opposed to signals. The systems discussed in this chapter are finite impulse response (FIR) digital filters. The term digital filter arises because these
More informationGENERALIZED DEFLATION ALGORITHMS FOR THE BLIND SOURCE-FACTOR SEPARATION OF MIMO-FIR CHANNELS. Mitsuru Kawamoto 1,2 and Yujiro Inouye 1
GENERALIZED DEFLATION ALGORITHMS FOR THE BLIND SOURCE-FACTOR SEPARATION OF MIMO-FIR CHANNELS Mitsuru Kawamoto,2 and Yuiro Inouye. Dept. of Electronic and Control Systems Engineering, Shimane University,
More informationAdaptive Inverse Control based on Linear and Nonlinear Adaptive Filtering
Adaptive Inverse Control based on Linear and Nonlinear Adaptive Filtering Bernard Widrow and Gregory L. Plett Department of Electrical Engineering, Stanford University, Stanford, CA 94305-9510 Abstract
More informationMultidimensional digital signal processing
PSfrag replacements Two-dimensional discrete signals N 1 A 2-D discrete signal (also N called a sequence or array) is a function 2 defined over thex(n set 1 of, n 2 ordered ) pairs of integers: y(nx 1,
More information(Refer Slide Time: )
Digital Signal Processing Prof. S. C. Dutta Roy Department of Electrical Engineering Indian Institute of Technology, Delhi FIR Lattice Synthesis Lecture - 32 This is the 32nd lecture and our topic for
More information4214 IEEE TRANSACTIONS ON SIGNAL PROCESSING, VOL. 54, NO. 11, NOVEMBER 2006
4214 IEEE TRANSACTIONS ON SIGNAL PROCESSING, VOL. 54, NO. 11, NOVEMBER 2006 Closed-Form Design of Generalized Maxflat R-Regular FIR M th-band Filters Using Waveform Moments Xi Zhang, Senior Member, IEEE,
More informationCounting Two-State Transition-Tour Sequences
Counting Two-State Transition-Tour Sequences Nirmal R. Saxena & Edward J. McCluskey Center for Reliable Computing, ERL 460 Department of Electrical Engineering, Stanford University, Stanford, CA 94305
More informationON THE REALIZATION OF 2D LATTICE-LADDER DISCRETE FILTERS
Journal of Circuits Systems and Computers Vol. 3 No. 5 (2004) 5 c World Scientific Publishing Company ON THE REALIZATION OF 2D LATTICE-LADDER DISCRETE FILTERS GEORGE E. ANTONIOU Department of Computer
More informationLet H(z) = P(z)/Q(z) be the system function of a rational form. Let us represent both P(z) and Q(z) as polynomials of z (not z -1 )
Review: Poles and Zeros of Fractional Form Let H() = P()/Q() be the system function of a rational form. Let us represent both P() and Q() as polynomials of (not - ) Then Poles: the roots of Q()=0 Zeros:
More informationIntroduction to Binary Convolutional Codes [1]
Introduction to Binary Convolutional Codes [1] Yunghsiang S. Han Graduate Institute of Communication Engineering, National Taipei University Taiwan E-mail: yshan@mail.ntpu.edu.tw Y. S. Han Introduction
More informationOptimal Polynomial Control for Discrete-Time Systems
1 Optimal Polynomial Control for Discrete-Time Systems Prof Guy Beale Electrical and Computer Engineering Department George Mason University Fairfax, Virginia Correspondence concerning this paper should
More informationResponses of Digital Filters Chapter Intended Learning Outcomes:
Responses of Digital Filters Chapter Intended Learning Outcomes: (i) Understanding the relationships between impulse response, frequency response, difference equation and transfer function in characterizing
More informationTwo-Dimensional Systems and Z-Transforms
CHAPTER 3 Two-Dimensional Systems and Z-Transforms In this chapter we look at the -D Z-transform. It is a generalization of the -D Z-transform used in the analysis and synthesis of -D linear constant coefficient
More information(i) Represent discrete-time signals using transform. (ii) Understand the relationship between transform and discrete-time Fourier transform
z Transform Chapter Intended Learning Outcomes: (i) Represent discrete-time signals using transform (ii) Understand the relationship between transform and discrete-time Fourier transform (iii) Understand
More informationECE503: Digital Signal Processing Lecture 6
ECE503: Digital Signal Processing Lecture 6 D. Richard Brown III WPI 20-February-2012 WPI D. Richard Brown III 20-February-2012 1 / 28 Lecture 6 Topics 1. Filter structures overview 2. FIR filter structures
More informationChapter Intended Learning Outcomes: (i) Understanding the relationship between transform and the Fourier transform for discrete-time signals
z Transform Chapter Intended Learning Outcomes: (i) Understanding the relationship between transform and the Fourier transform for discrete-time signals (ii) Understanding the characteristics and properties
More informationA Digit-Serial Systolic Multiplier for Finite Fields GF(2 m )
A Digit-Serial Systolic Multiplier for Finite Fields GF( m ) Chang Hoon Kim, Sang Duk Han, and Chun Pyo Hong Department of Computer and Information Engineering Taegu University 5 Naeri, Jinryang, Kyungsan,
More informationDigital Signal Processing Lecture 4
Remote Sensing Laboratory Dept. of Information Engineering and Computer Science University of Trento Via Sommarive, 14, I-38123 Povo, Trento, Italy Digital Signal Processing Lecture 4 Begüm Demir E-mail:
More informationUsing fractional delay to control the magnitudes and phases of integrators and differentiators
Using fractional delay to control the magnitudes and phases of integrators and differentiators M.A. Al-Alaoui Abstract: The use of fractional delay to control the magnitudes and phases of integrators and
More informationAlgebraic Algorithm for 2D Stability Test Based on a Lyapunov Equation. Abstract
Algebraic Algorithm for 2D Stability Test Based on a Lyapunov Equation Minoru Yamada Li Xu Osami Saito Abstract Some improvements have been proposed for the algorithm of Agathoklis such that 2D stability
More informationLecture 3 : Introduction to Binary Convolutional Codes
Lecture 3 : Introduction to Binary Convolutional Codes Binary Convolutional Codes 1. Convolutional codes were first introduced by Elias in 1955 as an alternative to block codes. In contrast with a block
More informationModule 4 : Laplace and Z Transform Problem Set 4
Module 4 : Laplace and Z Transform Problem Set 4 Problem 1 The input x(t) and output y(t) of a causal LTI system are related to the block diagram representation shown in the figure. (a) Determine a differential
More informationReview of Linear Systems Theory
Review of Linear Systems Theory The following is a (very) brief review of linear systems theory, convolution, and Fourier analysis. I work primarily with discrete signals, but each result developed in
More informationPassing from generating functions to recursion relations
Passing from generating functions to recursion relations D Klain last updated December 8, 2012 Comments and corrections are welcome In the textbook you are given a method for finding the generating function
More informationDigital Signal Processing Lecture 5
Remote Sensing Laboratory Dept. of Information Engineering and Computer Science University of Trento Via Sommarive, 14, I-38123 Povo, Trento, Italy Digital Signal Processing Lecture 5 Begüm Demir E-mail:
More informationLECTURE NOTES DIGITAL SIGNAL PROCESSING III B.TECH II SEMESTER (JNTUK R 13)
LECTURE NOTES ON DIGITAL SIGNAL PROCESSING III B.TECH II SEMESTER (JNTUK R 13) FACULTY : B.V.S.RENUKA DEVI (Asst.Prof) / Dr. K. SRINIVASA RAO (Assoc. Prof) DEPARTMENT OF ELECTRONICS AND COMMUNICATIONS
More informationDesign of Biorthogonal FIR Linear Phase Filter Banks with Structurally Perfect Reconstruction
Electronics and Communications in Japan, Part 3, Vol. 82, No. 1, 1999 Translated from Denshi Joho Tsushin Gakkai Ronbunshi, Vol. J81-A, No. 1, January 1998, pp. 17 23 Design of Biorthogonal FIR Linear
More informationAnalysis and Synthesis of Weighted-Sum Functions
Analysis and Synthesis of Weighted-Sum Functions Tsutomu Sasao Department of Computer Science and Electronics, Kyushu Institute of Technology, Iizuka 820-8502, Japan April 28, 2005 Abstract A weighted-sum
More informationDIGITAL SIGNAL PROCESSING UNIT III INFINITE IMPULSE RESPONSE DIGITAL FILTERS. 3.6 Design of Digital Filter using Digital to Digital
DIGITAL SIGNAL PROCESSING UNIT III INFINITE IMPULSE RESPONSE DIGITAL FILTERS Contents: 3.1 Introduction IIR Filters 3.2 Transformation Function Derivation 3.3 Review of Analog IIR Filters 3.3.1 Butterworth
More informationScattering Parameters
Berkeley Scattering Parameters Prof. Ali M. Niknejad U.C. Berkeley Copyright c 2016 by Ali M. Niknejad September 7, 2017 1 / 57 Scattering Parameters 2 / 57 Scattering Matrix Voltages and currents are
More information2. Typical Discrete-Time Systems All-Pass Systems (5.5) 2.2. Minimum-Phase Systems (5.6) 2.3. Generalized Linear-Phase Systems (5.
. Typical Discrete-Time Systems.1. All-Pass Systems (5.5).. Minimum-Phase Systems (5.6).3. Generalized Linear-Phase Systems (5.7) .1. All-Pass Systems An all-pass system is defined as a system which has
More informationIndeterminate Forms and L Hospital s Rule
APPLICATIONS OF DIFFERENTIATION Indeterminate Forms and L Hospital s Rule In this section, we will learn: How to evaluate functions whose values cannot be found at certain points. INDETERMINATE FORM TYPE
More informationISSN (Print) Research Article. *Corresponding author Nitin Rawal
Scholars Journal of Engineering and Technology (SJET) Sch. J. Eng. Tech., 016; 4(1):89-94 Scholars Academic and Scientific Publisher (An International Publisher for Academic and Scientific Resources) www.saspublisher.com
More informationHonours Advanced Algebra Unit 2: Polynomial Functions What s Your Identity? Learning Task (Task 8) Date: Period:
Honours Advanced Algebra Name: Unit : Polynomial Functions What s Your Identity? Learning Task (Task 8) Date: Period: Introduction Equivalent algebraic epressions, also called algebraic identities, give
More informationAsymptotic Stability Analysis of 2-D Discrete State Space Systems with Singular Matrix
Asymptotic Stability Analysis of 2-D Discrete State Space Systems with Singular Matri GUIDO IZUTA Department of Social Infmation Science Yonezawa Women s Juni College 6-15-1 Toi Machi, Yonezawa, Yamagata
More informationZ - Transform. It offers the techniques for digital filter design and frequency analysis of digital signals.
Z - Transform The z-transform is a very important tool in describing and analyzing digital systems. It offers the techniques for digital filter design and frequency analysis of digital signals. Definition
More informationEE 521: Instrumentation and Measurements
Aly El-Osery Electrical Engineering Department, New Mexico Tech Socorro, New Mexico, USA November 1, 2009 1 / 27 1 The z-transform 2 Linear Time-Invariant System 3 Filter Design IIR Filters FIR Filters
More informationModule 1: Signals & System
Module 1: Signals & System Lecture 6: Basic Signals in Detail Basic Signals in detail We now introduce formally some of the basic signals namely 1) The Unit Impulse function. 2) The Unit Step function
More informationOn homogeneous Zeilberger recurrences
Advances in Applied Mathematics 40 (2008) 1 7 www.elsevier.com/locate/yaama On homogeneous Zeilberger recurrences S.P. Polyakov Dorodnicyn Computing Centre, Russian Academy of Science, Vavilova 40, Moscow
More informationDESIGN OF QUANTIZED FIR FILTER USING COMPENSATING ZEROS
DESIGN OF QUANTIZED FIR FILTER USING COMPENSATING ZEROS Nivedita Yadav, O.P. Singh, Ashish Dixit Department of Electronics and Communication Engineering, Amity University, Lucknow Campus, Lucknow, (India)
More information21.4. Engineering Applications of z-transforms. Introduction. Prerequisites. Learning Outcomes
Engineering Applications of z-transforms 21.4 Introduction In this Section we shall apply the basic theory of z-transforms to help us to obtain the response or output sequence for a discrete system. This
More informationIntroduction to Techniques for Counting
Introduction to Techniques for Counting A generating function is a device somewhat similar to a bag. Instead of carrying many little objects detachedly, which could be embarrassing, we put them all in
More informationApproximate formulas for the Point-to-Ellipse and for the Point-to-Ellipsoid Distance Problem
Approimate formulas for the Point-to-Ellipse and for the Point-to-Ellipsoid Distance Problem ALEXEI UTESHEV St.Petersburg State University Department of Applied Mathematics Universitetskij pr. 35, 198504
More informationDigital Filter Structures. Basic IIR Digital Filter Structures. of an LTI digital filter is given by the convolution sum or, by the linear constant
Digital Filter Chapter 8 Digital Filter Block Diagram Representation Equivalent Basic FIR Digital Filter Basic IIR Digital Filter. Block Diagram Representation In the time domain, the input-output relations
More informationCosc 3451 Signals and Systems. What is a system? Systems Terminology and Properties of Systems
Cosc 3451 Signals and Systems Systems Terminology and Properties of Systems What is a system? an entity that manipulates one or more signals to yield new signals (often to accomplish a function) can be
More informationz-transforms Definition of the z-transform Chapter
z-transforms Chapter 7 In the study of discrete-time signal and systems, we have thus far considered the time-domain and the frequency domain. The z- domain gives us a third representation. All three domains
More information798 IEEE TRANSACTIONS ON CIRCUITS AND SYSTEMS II: ANALOG AND DIGITAL SIGNAL PROCESSING, VOL. 44, NO. 10, OCTOBER 1997
798 IEEE TRANSACTIONS ON CIRCUITS AND SYSTEMS II: ANALOG AND DIGITAL SIGNAL PROCESSING, VOL 44, NO 10, OCTOBER 1997 Stochastic Analysis of the Modulator Differential Pulse Code Modulator Rajesh Sharma,
More informationNew Design of Orthogonal Filter Banks Using the Cayley Transform
New Design of Orthogonal Filter Banks Using the Cayley Transform Jianping Zhou, Minh N. Do and Jelena Kovačević Department of Electrical and Computer Engineering University of Illinois at Urbana-Champaign,
More informationCOFINITE INDUCED SUBGRAPHS OF IMPARTIAL COMBINATORIAL GAMES: AN ANALYSIS OF CIS-NIM
#G INTEGERS 13 (013) COFINITE INDUCED SUBGRAPHS OF IMPARTIAL COMBINATORIAL GAMES: AN ANALYSIS OF CIS-NIM Scott M. Garrabrant 1 Pitzer College, Claremont, California coscott@math.ucla.edu Eric J. Friedman
More informationResearch Article Minor Prime Factorization for n-d Polynomial Matrices over Arbitrary Coefficient Field
Complexity, Article ID 6235649, 9 pages https://doi.org/10.1155/2018/6235649 Research Article Minor Prime Factorization for n-d Polynomial Matrices over Arbitrary Coefficient Field Jinwang Liu, Dongmei
More informationDesign of Stable IIR filters with prescribed flatness and approximately linear phase
Design of Stable IIR filters with prescribed flatness and approximately linear phase YASUNORI SUGITA Nagaoka University of Technology Dept. of Electrical Engineering Nagaoka city, Niigata-pref., JAPAN
More informationGeneralized Near-Bell Numbers
1 2 3 47 6 23 11 Journal of Integer Sequences, Vol. 12 2009, Article 09.5.7 Generalized Near-Bell Numbers Martin Griffiths Department of Mathematical Sciences University of Esse Wivenhoe Par Colchester
More informationExamples. 2-input, 1-output discrete-time systems: 1-input, 1-output discrete-time systems:
Discrete-Time s - I Time-Domain Representation CHAPTER 4 These lecture slides are based on "Digital Signal Processing: A Computer-Based Approach, 4th ed." textbook by S.K. Mitra and its instructor materials.
More informationUNIT-II Z-TRANSFORM. This expression is also called a one sided z-transform. This non causal sequence produces positive powers of z in X (z).
Page no: 1 UNIT-II Z-TRANSFORM The Z-Transform The direct -transform, properties of the -transform, rational -transforms, inversion of the transform, analysis of linear time-invariant systems in the -
More informationHonors Advanced Algebra Unit 2 Polynomial Operations September 14, 2016 Task 7: What s Your Identity?
Honors Advanced Algebra Name Unit Polynomial Operations September 14, 016 Task 7: What s Your Identity? MGSE9 1.A.APR.4 Prove polynomial identities and use them to describe numerical relationships. MGSE9
More informationOptimal Decentralized Control of Coupled Subsystems With Control Sharing
IEEE TRANSACTIONS ON AUTOMATIC CONTROL, VOL. 58, NO. 9, SEPTEMBER 2013 2377 Optimal Decentralized Control of Coupled Subsystems With Control Sharing Aditya Mahajan, Member, IEEE Abstract Subsystems that
More information7.3 Adding and Subtracting Rational Expressions
7.3 Adding and Subtracting Rational Epressions LEARNING OBJECTIVES. Add and subtract rational epressions with common denominators. 2. Add and subtract rational epressions with unlike denominators. 3. Add
More informationStability Condition in Terms of the Pole Locations
Stability Condition in Terms of the Pole Locations A causal LTI digital filter is BIBO stable if and only if its impulse response h[n] is absolutely summable, i.e., 1 = S h [ n] < n= We now develop a stability
More information1 Rational Exponents and Radicals
Introductory Algebra Page 1 of 11 1 Rational Eponents and Radicals 1.1 Rules of Eponents The rules for eponents are the same as what you saw earlier. Memorize these rules if you haven t already done so.
More informationAutomatic Stabilization of an Unmodeled Dynamical System Final Report
Automatic Stabilization of an Unmodeled Dynamical System: Final Report 1 Automatic Stabilization of an Unmodeled Dynamical System Final Report Gregory L. Plett and Clinton Eads May 2000. 1 Introduction
More informationMinimal positive realizations of transfer functions with nonnegative multiple poles
1 Minimal positive realizations of transfer functions with nonnegative multiple poles Béla Nagy Máté Matolcsi Béla Nagy is Professor at the Mathematics Department of Technical University, Budapest, e-mail:
More informationAPPLICATIONS OF DIFFERENTIATION
4 APPLICATIONS OF DIFFERENTIATION APPLICATIONS OF DIFFERENTIATION 4.4 Indeterminate Forms and L Hospital s Rule In this section, we will learn: How to evaluate functions whose values cannot be found at
More information3.8 Limits At Infinity
3.8. LIMITS AT INFINITY 53 Figure 3.5: Partial graph of f = /. We see here that f 0 as and as. 3.8 Limits At Infinity The its we introduce here differ from previous its in that here we are interested in
More information5.6 Asymptotes; Checking Behavior at Infinity
5.6 Asymptotes; Checking Behavior at Infinity checking behavior at infinity DEFINITION asymptote In this section, the notion of checking behavior at infinity is made precise, by discussing both asymptotes
More informationUse: Analysis of systems, simple convolution, shorthand for e jw, stability. Motivation easier to write. Or X(z) = Z {x(n)}
1 VI. Z Transform Ch 24 Use: Analysis of systems, simple convolution, shorthand for e jw, stability. A. Definition: X(z) = x(n) z z - transforms Motivation easier to write Or Note if X(z) = Z {x(n)} z
More informationCh. 7: Z-transform Reading
c J. Fessler, June 9, 3, 6:3 (student version) 7. Ch. 7: Z-transform Definition Properties linearity / superposition time shift convolution: y[n] =h[n] x[n] Y (z) =H(z) X(z) Inverse z-transform by coefficient
More informationDavid Weenink. First semester 2007
Institute of Phonetic Sciences University of Amsterdam First semester 2007 Digital s What is a digital filter? An algorithm that calculates with sample values Formant /machine H 1 (z) that: Given input
More informationDigital Filter Structures
Chapter 8 Digital Filter Structures 清大電機系林嘉文 cwlin@ee.nthu.edu.tw 03-5731152 8-1 Block Diagram Representation The convolution sum description of an LTI discrete-time system can, in principle, be used to
More informationMATH 116, LECTURES 10 & 11: Limits
MATH 6, LECTURES 0 & : Limits Limits In application, we often deal with quantities which are close to other quantities but which cannot be defined eactly. Consider the problem of how a car s speedometer
More informationSolutions to Math 41 First Exam October 12, 2010
Solutions to Math 41 First Eam October 12, 2010 1. 13 points) Find each of the following its, with justification. If the it does not eist, eplain why. If there is an infinite it, then eplain whether it
More informationIN neural-network training, the most well-known online
IEEE TRANSACTIONS ON NEURAL NETWORKS, VOL. 10, NO. 1, JANUARY 1999 161 On the Kalman Filtering Method in Neural-Network Training and Pruning John Sum, Chi-sing Leung, Gilbert H. Young, and Wing-kay Kan
More informationDigital Signal Processing, Homework 1, Spring 2013, Prof. C.D. Chung
Digital Signal Processing, Homework, Spring 203, Prof. C.D. Chung. (0.5%) Page 99, Problem 2.2 (a) The impulse response h [n] of an LTI system is known to be zero, except in the interval N 0 n N. The input
More informationVU Signal and Image Processing
052600 VU Signal and Image Processing Torsten Möller + Hrvoje Bogunović + Raphael Sahann torsten.moeller@univie.ac.at hrvoje.bogunovic@meduniwien.ac.at raphael.sahann@univie.ac.at vda.cs.univie.ac.at/teaching/sip/18s/
More informationTemporal Backpropagation for FIR Neural Networks
Temporal Backpropagation for FIR Neural Networks Eric A. Wan Stanford University Department of Electrical Engineering, Stanford, CA 94305-4055 Abstract The traditional feedforward neural network is a static
More informationTHEORY OF MIMO BIORTHOGONAL PARTNERS AND THEIR APPLICATION IN CHANNEL EQUALIZATION. Bojan Vrcelj and P. P. Vaidyanathan
THEORY OF MIMO BIORTHOGONAL PARTNERS AND THEIR APPLICATION IN CHANNEL EQUALIZATION Bojan Vrcelj and P P Vaidyanathan Dept of Electrical Engr 136-93, Caltech, Pasadena, CA 91125, USA E-mail: bojan@systemscaltechedu,
More informationSolution to Review Problems for Midterm #1
Solution to Review Problems for Midterm # Midterm I: Wednesday, September in class Topics:.,.3 and.-.6 (ecept.3) Office hours before the eam: Monday - and 4-6 p.m., Tuesday - pm and 4-6 pm at UH 080B)
More informationLecture 7 Discrete Systems
Lecture 7 Discrete Systems EE 52: Instrumentation and Measurements Lecture Notes Update on November, 29 Aly El-Osery, Electrical Engineering Dept., New Mexico Tech 7. Contents The z-transform 2 Linear
More informationPractical and Efficient Evaluation of Inverse Functions
J. C. HAYEN ORMATYC 017 TEXT PAGE A-1 Practical and Efficient Evaluation of Inverse Functions Jeffrey C. Hayen Oregon Institute of Technology (Jeffrey.Hayen@oit.edu) ORMATYC 017 J. C. HAYEN ORMATYC 017
More informationRadical Expressions and Functions What is a square root of 25? How many square roots does 25 have? Do the following square roots exist?
Topic 4 1 Radical Epressions and Functions What is a square root of 25? How many square roots does 25 have? Do the following square roots eist? 4 4 Definition: X is a square root of a if X² = a. 0 Symbolically,
More informationAbstract. 1 Introduction. 2 Idempotent filters. Idempotent Nonlinear Filters
Idempotent Nonlinear Filters R.K. Pearson and M. Gabbouj Tampere International Center for Signal Processing Tampere University of Technology P.O. Box 553, FIN-33101 Tampere, Finland E-mail: {pearson,gabbouj}@cs.tut.fi
More informationReview of Linear System Theory
Review of Linear System Theory The following is a (very) brief review of linear system theory and Fourier analysis. I work primarily with discrete signals. I assume the reader is familiar with linear algebra
More informationONE-DIMENSIONAL (1-D) two-channel FIR perfect-reconstruction
3542 IEEE TRANSACTIONS ON CIRCUITS AND SYSTEMS I: REGULAR PAPERS, VOL. 55, NO. 11, DECEMBER 2008 Eigenfilter Approach to the Design of One-Dimensional and Multidimensional Two-Channel Linear-Phase FIR
More informationLayered Polynomial Filter Structures
INFORMATICA, 2002, Vol. 13, No. 1, 23 36 23 2002 Institute of Mathematics and Informatics, Vilnius Layered Polynomial Filter Structures Kazys KAZLAUSKAS, Jaunius KAZLAUSKAS Institute of Mathematics and
More informationSection 3.3 Limits Involving Infinity - Asymptotes
76 Section. Limits Involving Infinity - Asymptotes We begin our discussion with analyzing its as increases or decreases without bound. We will then eplore functions that have its at infinity. Let s consider
More informationGaussian-Shaped Circularly-Symmetric 2D Filter Banks
Gaussian-Shaped Circularly-Symmetric D Filter Bans ADU MATEI Faculty of Electronics and Telecommunications Technical University of Iasi Bldv. Carol I no.11, Iasi 756 OMAIA Abstract: - In this paper we
More informationEuler-Maclaurin summation formula
Physics 4 Spring 6 Euler-Maclaurin summation formula Lecture notes by M. G. Rozman Last modified: March 9, 6 Euler-Maclaurin summation formula gives an estimation of the sum N in f i) in terms of the integral
More informationTransformation Techniques for Real Time High Speed Implementation of Nonlinear Algorithms
International Journal of Electronics and Communication Engineering. ISSN 0974-66 Volume 4, Number (0), pp.83-94 International Research Publication House http://www.irphouse.com Transformation Techniques
More informationSymmetric Wavelet Tight Frames with Two Generators
Symmetric Wavelet Tight Frames with Two Generators Ivan W. Selesnick Electrical and Computer Engineering Polytechnic University 6 Metrotech Center, Brooklyn, NY 11201, USA tel: 718 260-3416, fax: 718 260-3906
More informationMANY adaptive control methods rely on parameter estimation
610 IEEE TRANSACTIONS ON AUTOMATIC CONTROL, VOL 52, NO 4, APRIL 2007 Direct Adaptive Dynamic Compensation for Minimum Phase Systems With Unknown Relative Degree Jesse B Hoagg and Dennis S Bernstein Abstract
More informationMath 1314 Lesson 4 Limits
Math 1314 Lesson 4 Limits What is calculus? Calculus is the study of change, particularly, how things change over time. It gives us a framework for measuring change using some fairly simple models. In
More informationMA10103: Foundation Mathematics I. Lecture Notes Week 1
MA00: Foundation Mathematics I Lecture Notes Week Numbers The naturals are the nonnegative whole numbers, i.e., 0,,,, 4,.... The set of naturals is denoted by N. Warning: Sometimes only the positive integers
More informationInteger Sequences Related to Compositions without 2 s
1 2 3 47 6 23 11 Journal of Integer Sequences, Vol. 6 (2003), Article 03.2.3 Integer Sequences Related to Compositions without 2 s Phyllis Chinn Department of Mathematics Humboldt State University Arcata,
More information