Matrix power converters: spectra and stability
|
|
- Edwin Floyd
- 5 years ago
- Views:
Transcription
1 Matrix power converters: spectra and stability Stephen Cox School of Mathematical Sciences, University of Nottingham supported by EPSRC grant number EP/E018580/1 Making It Real Seminar, Bristol 2009 Stephen Cox Matrix power converters: spectra and stability 1/29
2 Outline What is a (matrix) power converter? Stephen Cox Matrix power converters: spectra and stability 2/29
3 Outline What is a (matrix) power converter? How does a power converter work? Stephen Cox Matrix power converters: spectra and stability 2/29
4 Outline What is a (matrix) power converter? How does a power converter work? I. How to work out the spectrum of a power converter Stephen Cox Matrix power converters: spectra and stability 2/29
5 Outline What is a (matrix) power converter? How does a power converter work? I. How to work out the spectrum of a power converter II. Instability of a matrix converter Stephen Cox Matrix power converters: spectra and stability 2/29
6 Power converters Power converters convert electrical power from one voltage and frequency to another voltage and frequency (typically 50Hz) AC AC DC AC AC DC DC DC Stephen Cox Matrix power converters: spectra and stability 3/29
7 Power converters Power converters convert electrical power from one voltage and frequency to another voltage and frequency (typically 50Hz) AC AC DC AC AC DC DC DC Applications: aircraft, ships, laptops (5V 3.3V conversion) Stephen Cox Matrix power converters: spectra and stability 3/29
8 Power converters Power converters convert electrical power from one voltage and frequency to another voltage and frequency (typically 50Hz) AC AC DC AC AC DC DC DC Applications: aircraft, ships, laptops (5V 3.3V conversion) Switching power converters use high frequency switching (typically 500kHz), and their output is rather complicated Stephen Cox Matrix power converters: spectra and stability 3/29
9 Power converters Power converters convert electrical power from one voltage and frequency to another voltage and frequency (typically 50Hz) AC AC DC AC AC DC DC DC Applications: aircraft, ships, laptops (5V 3.3V conversion) Switching power converters use high frequency switching (typically 500kHz), and their output is rather complicated Filtering is necessary to remove the high frequency components (strict regulatory requirements on electromagnetic interference; power quality) Stephen Cox Matrix power converters: spectra and stability 3/29
10 Power converters Power converters convert electrical power from one voltage and frequency to another voltage and frequency (typically 50Hz) AC AC DC AC AC DC DC DC Applications: aircraft, ships, laptops (5V 3.3V conversion) Switching power converters use high frequency switching (typically 500kHz), and their output is rather complicated Filtering is necessary to remove the high frequency components (strict regulatory requirements on electromagnetic interference; power quality) So we need to understand the spectrum of the signals from the power converter (for filter design) and its stability Stephen Cox Matrix power converters: spectra and stability 3/29
11 Part I: the frequency spectrum of a power converter Stephen Cox Matrix power converters: spectra and stability 4/29
12 A DC DC power converter How to convert 5V DC to 3.3V DC (efficiently)? Stephen Cox Matrix power converters: spectra and stability 5/29
13 A DC DC power converter How to convert 5V DC to 3.3V DC (efficiently)? 5V V(t) 3.3V 5 0 V t Switch rapidly between 0V (34%) and 5V (66%) 66% is the duty cycle There is some filtering at the output, for smoothing purposes Stephen Cox Matrix power converters: spectra and stability 5/29
14 A DC AC power converter How to convert ±1V DC to x sin Ωt AC? Stephen Cox Matrix power converters: spectra and stability 6/29
15 A DC AC power converter How to convert ±1V DC to x sin Ωt AC? +1V V(t) x sin Ω t 1 V t 1V 1 Switch rapidly between ±1V, with slowly varying duty cycle (pulse width modulation, PWM) Stephen Cox Matrix power converters: spectra and stability 6/29
16 A DC AC power converter How to convert ±1V DC to x sin Ωt AC? +1V V(t) x sin Ω t 1 V t 1V 1 Switch rapidly between ±1V, with slowly varying duty cycle (pulse width modulation, PWM) How to vary the duty cycle? What is the spectrum of the output? Stephen Cox Matrix power converters: spectra and stability 6/29
17 A DC AC power converter How to convert ±1V DC to x sin Ωt AC? +1V V(t) x sin Ω t 1 V t 1V 1 Switch rapidly between ±1V, with slowly varying duty cycle (pulse width modulation, PWM) How to vary the duty cycle? What is the spectrum of the output? Standard engineering technique: Black s method (1953) Here is an alternative, more compact method Stephen Cox Matrix power converters: spectra and stability 6/29
18 A DC AC power converter: modulation strategy 1 1 V n 1 A n 1 B n 1 n n+1 A n B n A n+1 n+2 B n+1 t Choose switching times to satisfy A n = n (1+x sin ΩA n) B n = n (3 x sin ΩB n) Stephen Cox Matrix power converters: spectra and stability 7/29
19 A DC AC power converter: modulation strategy 1 1 V n 1 A n 1 B n 1 n n+1 A n B n A n+1 n+2 B n+1 t Choose switching times to satisfy A n = n (1+x sin ΩA n) B n = n (3 x sin ΩB n) We want to calculate the Fourier spectrum of this square wave 1 1 V desired output triangular carrier wave t n 1 n n+1 n+2 A n 1 B n 1 A n B n A n+1 B n+1 Switching times are given by intersections of a highfrequency carrier wave and the desired output Stephen Cox Matrix power converters: spectra and stability 7/29
20 A DC AC power converter: modulation strategy 1 1 V n 1 A n 1 B n 1 n n+1 A n B n A n+1 n+2 B n+1 t Choose switching times to satisfy A n = n (1+x sin ΩA n) B n = n (3 x sin ΩB n) 1 ψ (t;t,t ) ψ 1 2 Notation: ψ(t; t 1, t 2 ) = top-hat function 0 t 1 t 2 t Stephen Cox Matrix power converters: spectra and stability 7/29
21 A DC AC power converter: modulation strategy 1 1 V n 1 A n 1 B n 1 n n+1 A n B n A n+1 n+2 B n+1 t Choose switching times to satisfy A n = n (1+x sin ΩA n) B n = n (3 x sin ΩB n) 1 ψ 0 (t;t,t ) ψ 1 2 t 1 t 2 t Notation: ψ(t; t 1, t 2 ) = top-hat function Then converter output is [ ] v(t) = ψ(t; B n, A n+1 ) ψ(t; A n, B n ) n= Stephen Cox Matrix power converters: spectra and stability 7/29
22 A DC AC power converter: modulation strategy 1 1 V n 1 A n 1 B n 1 n n+1 A n B n A n+1 n+2 B n+1 t Choose switching times to satisfy A n = n (1+x sin ΩA n) B n = n (3 x sin ΩB n) 1 ψ 0 (t;t,t ) ψ 1 2 t 1 t 2 t Notation: ψ(t; t 1, t 2 ) = top-hat function Then converter output is [ ] v(t) = ψ(t; B n, A n+1 ) ψ(t; A n, B n ) n= Poisson resummation: f(n) = v(t) = n= n= n= e 2πniτ f (τ) dτ ] e [ψ(t; 2πniτ B(τ), A(τ + 1)) ψ(t; A(τ), B(τ) dτ Stephen Cox Matrix power converters: spectra and stability 7/29
23 A DC AC power converter: calculating the spectrum v(t) = n= ] e [ψ(t; 2πniτ B(τ), A(τ + 1)) ψ(t; A(τ), B(τ)) dτ where A(τ) = τ (1 + x sin ΩA(τ)), B(τ) = τ (3 x sin ΩB(τ)) Stephen Cox Matrix power converters: spectra and stability 8/29
24 A DC AC power converter: calculating the spectrum v(t) = n= ] e [ψ(t; 2πniτ B(τ), A(τ + 1)) ψ(t; A(τ), B(τ)) dτ where A(τ) = τ (1 + x sin ΩA(τ)), B(τ) = τ (3 x sin ΩB(τ)) Consider e 2πniτ ψ(t; A(τ), B(τ)) dτ Stephen Cox Matrix power converters: spectra and stability 8/29
25 A DC AC power converter: calculating the spectrum v(t) = n= ] e [ψ(t; 2πniτ B(τ), A(τ + 1)) ψ(t; A(τ), B(τ)) dτ where A(τ) = τ (1 + x sin ΩA(τ)), B(τ) = τ (3 x sin ΩB(τ)) Consider e 2πniτ ψ(t; A(τ), B(τ)) dτ We know that ψ(t; A(τ), B(τ)) = 1 when A(τ) < t < B(τ) Stephen Cox Matrix power converters: spectra and stability 8/29
26 A DC AC power converter: calculating the spectrum v(t) = n= ] e [ψ(t; 2πniτ B(τ), A(τ + 1)) ψ(t; A(τ), B(τ)) dτ where A(τ) = τ (1 + x sin ΩA(τ)), B(τ) = τ (3 x sin ΩB(τ)) Consider e 2πniτ ψ(t; A(τ), B(τ)) dτ We know that ψ(t; A(τ), B(τ)) = 1 when A(τ) < t < B(τ) So if we introduce A(t) and B(t) such that t = A(τ) τ = A(t), t = B(τ) τ = B(t) then ψ(t; A(τ), B(τ)) = 1 when B(t) < τ < A(t) Stephen Cox Matrix power converters: spectra and stability 8/29
27 A DC AC power converter: calculating the spectrum v(t) = n= ] e [ψ(t; 2πniτ B(τ), A(τ + 1)) ψ(t; A(τ), B(τ)) dτ where A(τ) = τ (1 + x sin ΩA(τ)), B(τ) = τ (3 x sin ΩB(τ)) Consider e 2πniτ ψ(t; A(τ), B(τ)) dτ We know that ψ(t; A(τ), B(τ)) = 1 when A(τ) < t < B(τ) So if we introduce A(t) and B(t) such that t = A(τ) τ = A(t), t = B(τ) τ = B(t) then ψ(t; A(τ), B(τ)) = 1 when B(t) < τ < A(t) [ ] Hence v(t) = (πni) 1 e 2πniB(t) e 2πniA(t) n= Stephen Cox Matrix power converters: spectra and stability 8/29
28 A DC AC power converter: calculating the spectrum But A(t) = t 1 4 (1 + x sin Ωt), B(t) = t 1 4 (3 x sin Ωt), so v(t) = n= e 2πnit πni [i n e (πnx/2)i sinωt ( i) n e (πnx/2)i sin Ωt ] and we have the Jacobi formula e iz sin θ = J m (z)e iθ m= Stephen Cox Matrix power converters: spectra and stability 9/29
29 A DC AC power converter: calculating the spectrum But A(t) = t 1 4 (1 + x sin Ωt), B(t) = t 1 4 (3 x sin Ωt), so e 2πnit ] v(t) = [i n e (πnx/2)i sinωt ( i) n e (πnx/2)i sin Ωt πni = mn n= v mn e iωmnt where v mn = (πni) 1 i n (( 1) m+n 1)J m (πnx/2) for n 0 and Ω mn = 2πn + mω Stephen Cox Matrix power converters: spectra and stability 9/29
30 A DC AC power converter: calculating the spectrum But A(t) = t 1 4 (1 + x sin Ωt), B(t) = t 1 4 (3 x sin Ωt), so e 2πnit ] v(t) = [i n e (πnx/2)i sinωt ( i) n e (πnx/2)i sin Ωt πni = mn n= v mn e iωmnt where v mn = (πni) 1 i n (( 1) m+n 1)J m (πnx/2) for n 0 and Ω mn = 2πn + mω Special case: v m0 = 1 2 xi for (m = ±1); v m0 = 0 otherwise Stephen Cox Matrix power converters: spectra and stability 9/29
31 A DC AC power converter: calculating the spectrum But A(t) = t 1 4 (1 + x sin Ωt), B(t) = t 1 4 (3 x sin Ωt), so e 2πnit ] v(t) = [i n e (πnx/2)i sinωt ( i) n e (πnx/2)i sin Ωt πni = mn n= v mn e iωmnt where v mn = (πni) 1 i n (( 1) m+n 1)J m (πnx/2) for n 0 and Ω mn = 2πn + mω Special case: v m0 = 1 2 xi for (m = ±1); v m0 = 0 otherwise The low-frequency part of the output is exactly x sin Ωt! Stephen Cox Matrix power converters: spectra and stability 9/29
32 Conclusions (on spectra) There is a compact way to determine the spectrum for switching power converters, much better than the engineering default (Black s method) Stephen Cox Matrix power converters: spectra and stability 10/29
33 Conclusions (on spectra) There is a compact way to determine the spectrum for switching power converters, much better than the engineering default (Black s method) We are currently developing the method for other power converters and modulation strategies Stephen Cox Matrix power converters: spectra and stability 10/29
34 Conclusions (on spectra) There is a compact way to determine the spectrum for switching power converters, much better than the engineering default (Black s method) We are currently developing the method for other power converters and modulation strategies Current spectra can also be found using the new method Stephen Cox Matrix power converters: spectra and stability 10/29
35 Part II: the stability of matrix power converters Stephen Cox Matrix power converters: spectra and stability 11/29
36 The matrix converter An AC power supply is generally delivered as a three-phase supply x sin Ωt x sin( Ωt+2 π/3) x sin( Ωt 2 π/3) 0V Stephen Cox Matrix power converters: spectra and stability 12/29
37 The matrix converter An AC power supply is generally delivered as a three-phase supply x sin Ωt x sin( Ωt+2 π/3) x sin( Ωt 2 π/3) 0V v A v B v C v a matrix converter v b v c A matrix converter converts between one three-phase power supply and another Inputs: A, B, C Outputs: a, b, c Stephen Cox Matrix power converters: spectra and stability 12/29
38 Matrix converter: modulation strategy Each output is connected in sequence to each of the input lines A a then B a then C a V a a simple modulation strategy Aa n An Bn n+1 Ba Ca t Stephen Cox Matrix power converters: spectra and stability 13/29
39 Matrix converter: modulation strategy Each output is connected in sequence to each of the input lines A a then B a then C a V a a simple modulation strategy n An Bn n+1 Choose switching times so that the low-frequency components of the outputs are the intended new three-phase supply Aa Ba Ca t Stephen Cox Matrix power converters: spectra and stability 13/29
40 Matrix converter: modulation strategy Each output is connected in sequence to each of the input lines A a then B a then C a V a a simple modulation strategy n An Bn n+1 Choose switching times so that the low-frequency components of the outputs are the intended new three-phase supply Full spectrum can be calculated: input/output voltage/current [SM Cox and SC Creagh, 2009, SIAM J Appl Math] Aa Ba Ca t Stephen Cox Matrix power converters: spectra and stability 13/29
41 Power converters: stability controller power supply filter power converter filter/ load But in reality there are filters at the input and output Stephen Cox Matrix power converters: spectra and stability 14/29
42 Power converters: stability controller power supply filter power converter filter/ load But in reality there are filters at the input and output Current drawn by the load leads to a discrepancy between the voltage seen by the controller and the power supply voltage Stephen Cox Matrix power converters: spectra and stability 14/29
43 Power converters: stability controller power supply filter power converter filter/ load But in reality there are filters at the input and output Current drawn by the load leads to a discrepancy between the voltage seen by the controller and the power supply voltage This in turn affects the output currents, which further influences the power converter controller, leading to instability Stephen Cox Matrix power converters: spectra and stability 14/29
44 Power converters: stability controller power supply filter power converter filter/ load But in reality there are filters at the input and output Current drawn by the load leads to a discrepancy between the voltage seen by the controller and the power supply voltage This in turn affects the output currents, which further influences the power converter controller, leading to instability Controller delays can also lead to (or modify) instability Stephen Cox Matrix power converters: spectra and stability 14/29
45 Power converters: stability controller power supply filter power converter filter/ load But in reality there are filters at the input and output Current drawn by the load leads to a discrepancy between the voltage seen by the controller and the power supply voltage This in turn affects the output currents, which further influences the power converter controller, leading to instability Controller delays can also lead to (or modify) instability This instability can be catastrophic in applications! Stephen Cox Matrix power converters: spectra and stability 14/29
46 Matrix converter: averaged model ω i R 2 i i digital controller i o ω o v eq R L 1 1 L 2 C v i matrix converter R v o L 3 3 voltage supply input filter load This diagram shows one input phase and one output phase: in practice there are three inputs and three outputs Stephen Cox Matrix power converters: spectra and stability 15/29
47 Matrix converter: averaged model ω i R 2 i i digital controller i o ω o v eq R L 1 1 L 2 C v i matrix converter R v o L 3 3 voltage supply input filter load Simplest model averages over the switching: duty cycles are specified, but individual switch commutations are not modelled V a Aa discretely switched voltages Ba Ca t averaged Stephen Cox Matrix power converters: spectra and stability 15/29
48 Matrix converter: averaged model ω i R 2 i i digital controller i o ω o v eq R L 1 1 L 2 C v i matrix converter R v o L 3 3 voltage supply input filter load Simplest model averages over the switching: duty cycles are specified, but individual switch commutations are not modelled Introduce space vectors, e.g. 2 3 ( v A (t) + e 2πi/3 v B (t) + e 2πi/3 v C (t) V a Aa discretely switched voltages Ba Ca t averaged ) = g(t) exp iω i t, so the complex function g(t) represents the input voltages, etc. Stephen Cox Matrix power converters: spectra and stability 15/29
49 Matrix converter: averaged model Then the governing ODE for g(t) is ( ) 2P X 3g + Yg(t) = YV eq (t) where X f = R 1 R 2 f +(R 1 L 2 +R 2 L 1 +R 2 L 2 ) ( iω i + d ) ( f +L 1 L 2 iω i + d ) 2 f dt dt and ( Yf = R 2 f + (R 1 R 2 C + L 2 ) iω i + d ) f dt ( + (R 1 L 2 + R 2 L 1 + R 2 L 2 )C iω i + d ) 2 ( f + L 1 L 2 C iω i + d ) 3 f dt dt and P = input power = output power Stephen Cox Matrix power converters: spectra and stability 16/29
50 Matrix converter: averaged model supply filter load R 1 = 0.55Ω R 2 = 300Ω R 3 = 8.2Ω L 1 = 0.90 mh L 2 = 1.16 mh L 3 = 1.3 mh V eq = V C = 4.5µF ω o = 2π 100 rad/s ω i = 2π 50 rad/s D. Casadei, G. Serra, A. Tani, A. Trentin, L. Zarri Theoretical and experimental investigation on the stability of matrix converters. IEEE Trans Industr Electr (2005). 50Hz input 100Hz output Stephen Cox Matrix power converters: spectra and stability 17/29
51 Matrix converter: averaged model Bifurcation parameter is power P or voltage transfer ratio q = reference output voltage input voltage Stephen Cox Matrix power converters: spectra and stability 18/29
52 Matrix converter: averaged model Bifurcation parameter is power P or voltage transfer ratio q = reference output voltage input voltage Results The steady-state operating point is g = constant Stephen Cox Matrix power converters: spectra and stability 18/29
53 Matrix converter: averaged model Bifurcation parameter is power P or voltage transfer ratio q = reference output voltage input voltage Results The steady-state operating point is g = constant The steady-state is stable provided q < q c Stephen Cox Matrix power converters: spectra and stability 18/29
54 Matrix converter: averaged model Bifurcation parameter is power P or voltage transfer ratio q = reference output voltage input voltage Results The steady-state operating point is g = constant The steady-state is stable provided q < q c At q = q c there is a Hopf bifurcation and the solution develops ripple at frequency approx 1651Hz (Typical switching frequency 12.5kHz) Stephen Cox Matrix power converters: spectra and stability 18/29
55 Matrix converter: bifurcation to ripple A weakly nonlinear expansion of the solution near the Hopf bifurcation shows that this bifurcation is strongly subcritical input voltage weakly nonlinear solution Hopf bifn solution with ripple steady state output voltage Results from AUTO (checked with home-made code) Stephen Cox Matrix power converters: spectra and stability 19/29
56 Matrix converter: bifurcation to ripple A weakly nonlinear expansion of the solution near the Hopf bifurcation shows that this bifurcation is strongly subcritical input voltage weakly nonlinear solution Hopf bifn solution with ripple steady state output voltage A start-up transient could lead to catastrophic failure, even at around 50% of the linear stability threshold Stephen Cox Matrix power converters: spectra and stability 19/29
57 Matrix converter: bifurcation to ripple Evolution of disturbances to the steady-state solution, just above threshold (28V>26.88V) 300 g t Catastrophic failure! Stephen Cox Matrix power converters: spectra and stability 20/29
58 Matrix converter: nonlinear ripple Eventually we cannot continue the solution branch, at input voltage Hopf bifn solution with ripple steady state output voltage Stephen Cox Matrix power converters: spectra and stability 21/29
59 Matrix converter: nonlinear ripple Eventually we cannot continue the solution branch, at input voltage Hopf bifn solution with ripple steady state output voltage 400 The solution develops an input current spike when the input voltage f(t) g(t) is close to zero 0 one period of the ripple Stephen Cox Matrix power converters: spectra and stability 21/29
60 Matrix converter: model foundations The sharp current spike occurs over a short fraction of the ripple period Stephen Cox Matrix power converters: spectra and stability 22/29
61 Matrix converter: model foundations The sharp current spike occurs over a short fraction of the ripple period This stretches the assumption that we can ignore the fast switching, and undermines our averaged model Stephen Cox Matrix power converters: spectra and stability 22/29
62 Matrix converter: model foundations The sharp current spike occurs over a short fraction of the ripple period This stretches the assumption that we can ignore the fast switching, and undermines our averaged model To understand the postinstability behaviour of the matrix converter we need to consider the details of the switching itself V a Aa discretely switched voltages Ba Ca t averaged Stephen Cox Matrix power converters: spectra and stability 22/29
63 Matrix converter: nonaveraged model ω i R 2 i i digital controller i o ω o v eq R L 1 1 L 2 C v i matrix converter R v o L 3 3 voltage supply input filter load Introduce vectors v A v i = v B v o = v C v a v b v c i i = i A i B i C i o = i a i b i c Stephen Cox Matrix power converters: spectra and stability 23/29
64 Matrix converter: nonaveraged model ω i R 2 i i digital controller i o ω o v eq R L 1 1 L 2 C v i matrix converter R v o L 3 3 voltage supply input filter load Input: X i i + Y(v i s) = 0 where X f = R 1 R 2 f + (R 1 L 2 + R 2 L 1 + R 2 L 2 ) df dt + L d 2 f 1L 2 dt 2 and Yf = R 2 f +(R 1 R 2 C +L 2 ) df dt +(R 1L 2 +R 2 L 1 +R 2 L 2 )C d2 f dt 2 +L 1L 2 C d3 f dt 3 and s represents the supply voltage Stephen Cox Matrix power converters: spectra and stability 23/29
65 Matrix converter: nonaveraged model ω i R 2 i i digital controller i o ω o v eq R L 1 1 L 2 C v i matrix converter R v o L 3 3 voltage supply input filter load Input: X i i + Y(v i s) = 0 where X f = R 1 R 2 f + (R 1 L 2 + R 2 L 1 + R 2 L 2 ) df dt + L d 2 f 1L 2 dt 2 and Yf = R 2 f +(R 1 R 2 C +L 2 ) df dt +(R 1L 2 +R 2 L 1 +R 2 L 2 )C d2 f dt 2 +L 1L 2 C d3 f dt 3 Output: v o = R 3 i o + L 3 di o dt Stephen Cox Matrix power converters: spectra and stability 23/29
66 Matrix converter: nonaveraged model Can characterise the state of the system by the vector x(t) = v i v i v i i o V a Aa n An Bn n+1 Ba Ca t Stephen Cox Matrix power converters: spectra and stability 24/29
67 Matrix converter: nonaveraged model Can characterise the state of the system by the vector x(t) = v i v i v i i o Then the switching model is the ODE system V a Aa Ca n An Bn n+1 Ba t dx dt = A(t)x(t) + f (t) where f represents the power supply and A(t) is a piecewise-constant matrix which encodes the linear voltage current relations and the discrete switching v A v B v C v a matrix converter v b v c Stephen Cox Matrix power converters: spectra and stability 24/29
68 Matrix converter: nonaveraged model The system dx = A(t)x + f has dt piecewise-constant coefficients, and so can be solved exactly between switch commutations V a Aa n An Bn n+1 Ba Ca t Stephen Cox Matrix power converters: spectra and stability 25/29
69 Matrix converter: nonaveraged model The system dx = A(t)x + f has dt piecewise-constant coefficients, and so can be solved exactly between switch commutations V a n An Bn n+1 But x is not continuous at switch commutations ( v i and v i ) Aa Ba Ca t Stephen Cox Matrix power converters: spectra and stability 25/29
70 Matrix converter: nonaveraged model The system dx = A(t)x + f has dt piecewise-constant coefficients, and so can be solved exactly between switch commutations V a n An Bn n+1 But x is not continuous at switch commutations ( v i and v i ) So at each switch commutation, we impose continuity of capacitor voltages and inductor currents, leading to jump conditions on x Aa Ba Ca t Stephen Cox Matrix power converters: spectra and stability 25/29
71 Matrix converter: nonaveraged model The system dx = A(t)x + f has dt piecewise-constant coefficients, and so can be solved exactly between switch commutations V a n An Bn n+1 But x is not continuous at switch commutations ( v i and v i ) So at each switch commutation, we impose continuity of capacitor voltages and inductor currents, leading to jump conditions on x Use regular sampling of the inputs to determine switching times Aa Ba Ca t Stephen Cox Matrix power converters: spectra and stability 25/29
72 Matrix converter: nonaveraged model The system dx = A(t)x + f has dt piecewise-constant coefficients, and so can be solved exactly between switch commutations V a n An Bn n+1 But x is not continuous at switch commutations ( v i and v i ) So at each switch commutation, we impose continuity of capacitor voltages and inductor currents, leading to jump conditions on x Use regular sampling of the inputs to determine switching times How does the behaviour of the nonaveraged model compare with that of the averaged model? Aa Ba Ca t Stephen Cox Matrix power converters: spectra and stability 25/29
73 Nonaveraged model results Start near steady-state operating point and simulate model for various voltage transfer ratios q and switching periods T q c averaged model steady state unstable T steady state stable Stephen Cox Matrix power converters: spectra and stability 26/29
74 Nonaveraged model results Start near steady-state operating point and simulate model for various voltage transfer ratios q and switching periods T q c averaged model steady state unstable T steady state stable As for the averaged model, q > q c gives instability to ripple But now q c = q c (T ) Stephen Cox Matrix power converters: spectra and stability 26/29
75 Nonaveraged model results v2 + v2 B + v2 A C t Above threshold there is catastrophic failure, as in the averaged model Stephen Cox Matrix power converters: spectra and stability 27/29
76 Nonaveraged model results q c averaged model steady state unstable T steady state stable Stephen Cox Matrix power converters: spectra and stability 28/29
77 Nonaveraged model results q c averaged model steady state unstable T steady state stable Instability threshold tends to that of averaged model as T 0 Stephen Cox Matrix power converters: spectra and stability 28/29
78 Nonaveraged model results q c averaged model steady state unstable T steady state stable Instability threshold tends to that of averaged model as T 0 Instability threshold q c (T ) is significantly below q c (0) for sufficiently rapid switching! Stephen Cox Matrix power converters: spectra and stability 28/29
79 Conclusions Power converters are an important technology, and mathematical modelling currently lags behind applications Stephen Cox Matrix power converters: spectra and stability 29/29
80 Conclusions Power converters are an important technology, and mathematical modelling currently lags behind applications Matrix converters are an emerging technology for converting AC AC Stephen Cox Matrix power converters: spectra and stability 29/29
81 Conclusions Power converters are an important technology, and mathematical modelling currently lags behind applications Matrix converters are an emerging technology for converting AC AC A model averaged over a switching period shows that matrix converters can become unstable in a subcritical bifurcation to a branch of solutions with ripple Stephen Cox Matrix power converters: spectra and stability 29/29
82 Conclusions Power converters are an important technology, and mathematical modelling currently lags behind applications Matrix converters are an emerging technology for converting AC AC A model averaged over a switching period shows that matrix converters can become unstable in a subcritical bifurcation to a branch of solutions with ripple Averaged model significantly overestimates threshold for instability; our full switching model gives the threshold Stephen Cox Matrix power converters: spectra and stability 29/29
83 Conclusions Power converters are an important technology, and mathematical modelling currently lags behind applications Matrix converters are an emerging technology for converting AC AC A model averaged over a switching period shows that matrix converters can become unstable in a subcritical bifurcation to a branch of solutions with ripple Averaged model significantly overestimates threshold for instability; our full switching model gives the threshold What about more realistic modulation strategies? Stephen Cox Matrix power converters: spectra and stability 29/29
84 Conclusions Power converters are an important technology, and mathematical modelling currently lags behind applications Matrix converters are an emerging technology for converting AC AC A model averaged over a switching period shows that matrix converters can become unstable in a subcritical bifurcation to a branch of solutions with ripple Averaged model significantly overestimates threshold for instability; our full switching model gives the threshold What about more realistic modulation strategies? Delays in the controller? Losses (etc) in the converter? Stephen Cox Matrix power converters: spectra and stability 29/29
85 Conclusions Power converters are an important technology, and mathematical modelling currently lags behind applications Matrix converters are an emerging technology for converting AC AC A model averaged over a switching period shows that matrix converters can become unstable in a subcritical bifurcation to a branch of solutions with ripple Averaged model significantly overestimates threshold for instability; our full switching model gives the threshold What about more realistic modulation strategies? Delays in the controller? Losses (etc) in the converter? Can the catastrophic failure be tamed? Stephen Cox Matrix power converters: spectra and stability 29/29
Mathematical models for class-d amplifiers
Mathematical models for class-d amplifiers Stephen Cox School of Mathematical Sciences, University of Nottingham, UK 12 November 2012 Stephen Cox Mathematical models for class-d amplifiers 1/38 Background
More informationET4119 Electronic Power Conversion 2011/2012 Solutions 27 January 2012
ET4119 Electronic Power Conversion 2011/2012 Solutions 27 January 2012 1. In the single-phase rectifier shown below in Fig 1a., s = 1mH and I d = 10A. The input voltage v s has the pulse waveform shown
More informationAinslie-Malik, Gregory R. (2013) Mathematical analysis of PWM processes. PhD thesis, University of Nottingham.
Ainslie-Malik, Gregory R. (203) Mathematical analysis of PWM processes. PhD thesis, University of Nottingham. Access from the University of Nottingham repository: http://eprints.nottingham.ac.uk/302//mathematical_analysis_of_pwm_processes.pdf
More informationHandout 11: AC circuit. AC generator
Handout : AC circuit AC generator Figure compares the voltage across the directcurrent (DC) generator and that across the alternatingcurrent (AC) generator For DC generator, the voltage is constant For
More informationAC analysis. EE 201 AC analysis 1
AC analysis Now we turn to circuits with sinusoidal sources. Earlier, we had a brief look at sinusoids, but now we will add in capacitors and inductors, making the story much more interesting. What are
More informationCh 6.4: Differential Equations with Discontinuous Forcing Functions
Ch 6.4: Differential Equations with Discontinuous Forcing Functions! In this section focus on examples of nonhomogeneous initial value problems in which the forcing function is discontinuous. Example 1:
More informationEECE 2150 Circuits and Signals Final Exam Fall 2016 Dec 16
EECE 2150 Circuits and Signals Final Exam Fall 2016 Dec 16 Instructions: Write your name and section number on all pages Closed book, closed notes; Computers and cell phones are not allowed You can use
More informationGATE EE Topic wise Questions SIGNALS & SYSTEMS
www.gatehelp.com GATE EE Topic wise Questions YEAR 010 ONE MARK Question. 1 For the system /( s + 1), the approximate time taken for a step response to reach 98% of the final value is (A) 1 s (B) s (C)
More informationREACTANCE. By: Enzo Paterno Date: 03/2013
REACTANCE REACTANCE By: Enzo Paterno Date: 03/2013 5/2007 Enzo Paterno 1 RESISTANCE - R i R (t R A resistor for all practical purposes is unaffected by the frequency of the applied sinusoidal voltage or
More informationChapter 33. Alternating Current Circuits
Chapter 33 Alternating Current Circuits 1 Capacitor Resistor + Q = C V = I R R I + + Inductance d I Vab = L dt AC power source The AC power source provides an alternative voltage, Notation - Lower case
More informationAlternating Currents. The power is transmitted from a power house on high voltage ac because (a) Electric current travels faster at higher volts (b) It is more economical due to less power wastage (c)
More informationDriven RLC Circuits Challenge Problem Solutions
Driven LC Circuits Challenge Problem Solutions Problem : Using the same circuit as in problem 6, only this time leaving the function generator on and driving below resonance, which in the following pairs
More informationEE292: Fundamentals of ECE
EE292: Fundamentals of ECE Fall 2012 TTh 10:00-11:15 SEB 1242 Lecture 20 121101 http://www.ee.unlv.edu/~b1morris/ee292/ 2 Outline Chapters 1-3 Circuit Analysis Techniques Chapter 10 Diodes Ideal Model
More informationECE2262 Electric Circuits. Chapter 6: Capacitance and Inductance
ECE2262 Electric Circuits Chapter 6: Capacitance and Inductance Capacitors Inductors Capacitor and Inductor Combinations Op-Amp Integrator and Op-Amp Differentiator 1 CAPACITANCE AND INDUCTANCE Introduces
More informationModeling Buck Converter by Using Fourier Analysis
PIERS ONLINE, VOL. 6, NO. 8, 2010 705 Modeling Buck Converter by Using Fourier Analysis Mao Zhang 1, Weiping Zhang 2, and Zheng Zhang 2 1 School of Computing, Engineering and Physical Sciences, University
More informationStability Analysis of Single-Phase Grid-Feeding Inverters with PLL using Harmonic Linearisation and Linear Time Periodic (LTP) Theory
Stability Analysis of Single-Phase Grid-Feeding Inverters with PLL using Harmonic Linearisation and Linear Time Periodic (LTP) Theory Valerio Salis, Alessandro Costabeber, Pericle Zanchetta Power Electronics,
More informationRegulated DC-DC Converter
Regulated DC-DC Converter Zabir Ahmed Lecturer, BUET Jewel Mohajan Lecturer, BUET M A Awal Graduate Research Assistant NSF FREEDM Systems Center NC State University Former Lecturer, BUET 1 Problem Statement
More informationELECTROMAGNETIC OSCILLATIONS AND ALTERNATING CURRENT
Chapter 31: ELECTROMAGNETIC OSCILLATIONS AND ALTERNATING CURRENT 1 A charged capacitor and an inductor are connected in series At time t = 0 the current is zero, but the capacitor is charged If T is the
More informationFourier series. XE31EO2 - Pavel Máša. Electrical Circuits 2 Lecture1. XE31EO2 - Pavel Máša - Fourier Series
Fourier series Electrical Circuits Lecture - Fourier Series Filtr RLC defibrillator MOTIVATION WHAT WE CAN'T EXPLAIN YET Source voltage rectangular waveform Resistor voltage sinusoidal waveform - Fourier
More informationUsing Simulink to analyze 2 degrees of freedom system
Using Simulink to analyze 2 degrees of freedom system Nasser M. Abbasi Spring 29 page compiled on June 29, 25 at 4:2pm Abstract A two degrees of freedom system consisting of two masses connected by springs
More informationMath Ordinary Differential Equations
Math 411 - Ordinary Differential Equations Review Notes - 1 1 - Basic Theory A first order ordinary differential equation has the form x = f(t, x) (11) Here x = dx/dt Given an initial data x(t 0 ) = x
More informationLecture 4: R-L-C Circuits and Resonant Circuits
Lecture 4: R-L-C Circuits and Resonant Circuits RLC series circuit: What's V R? Simplest way to solve for V is to use voltage divider equation in complex notation: V X L X C V R = in R R + X C + X L L
More informationSimple Time Domain Analysis of a 4-Level H-bridge Flying Capacitor Converter Voltage Balancing
Simple Time Domain Analysis of a 4-evel H-bridge Flying Capacitor Converter Voltage Balancing Steven Thielemans Alex uderman Boris eznikov and Jan Melkebeek Electrical Energy Systems and Automation Department
More informationALTERNATING CURRENT. with X C = 0.34 A. SET UP: The specified value is the root-mean-square current; I. EXECUTE: (a) V = (0.34 A) = 0.12 A.
ATENATING UENT 3 3 IDENTIFY: i Icosωt and I I/ SET UP: The specified value is the root-mean-square current; I 34 A EXEUTE: (a) I 34 A (b) I I (34 A) 48 A (c) Since the current is positive half of the time
More informationInducing Chaos in the p/n Junction
Inducing Chaos in the p/n Junction Renato Mariz de Moraes, Marshal Miller, Alex Glasser, Anand Banerjee, Ed Ott, Tom Antonsen, and Steven M. Anlage CSR, Department of Physics MURI Review 14 November, 2003
More informationmywbut.com Lesson 16 Solution of Current in AC Parallel and Seriesparallel
esson 6 Solution of urrent in Parallel and Seriesparallel ircuits n the last lesson, the following points were described:. How to compute the total impedance/admittance in series/parallel circuits?. How
More informationElectric Circuit Theory
Electric Circuit Theory Nam Ki Min nkmin@korea.ac.kr 010-9419-2320 Chapter 11 Sinusoidal Steady-State Analysis Nam Ki Min nkmin@korea.ac.kr 010-9419-2320 Contents and Objectives 3 Chapter Contents 11.1
More informationChapter 10: Sinusoids and Phasors
Chapter 10: Sinusoids and Phasors 1. Motivation 2. Sinusoid Features 3. Phasors 4. Phasor Relationships for Circuit Elements 5. Impedance and Admittance 6. Kirchhoff s Laws in the Frequency Domain 7. Impedance
More informationEE292: Fundamentals of ECE
EE292: Fundamentals of ECE Fall 2012 TTh 10:00-11:15 SEB 1242 Lecture 14 121011 http://www.ee.unlv.edu/~b1morris/ee292/ 2 Outline Review Steady-State Analysis RC Circuits RL Circuits 3 DC Steady-State
More informationCourse Updates. Reminders: 1) Assignment #10 due Today. 2) Quiz # 5 Friday (Chap 29, 30) 3) Start AC Circuits
ourse Updates http://www.phys.hawaii.edu/~varner/phys272-spr10/physics272.html eminders: 1) Assignment #10 due Today 2) Quiz # 5 Friday (hap 29, 30) 3) Start A ircuits Alternating urrents (hap 31) In this
More informationEECE 2150 Circuits and Signals Final Exam Fall 2016 Dec 12
EECE 2150 Circuits and Signals Final Exam Fall 2016 Dec 12 Instructions: Write your name and section number on all pages Closed book, closed notes; Computers and cell phones are not allowed You can use
More informationLECTURE 8 Fundamental Models of Pulse-Width Modulated DC-DC Converters: f(d)
1 ECTURE 8 Fundamental Models of Pulse-Width Modulated DC-DC Converters: f(d) I. Quasi-Static Approximation A. inear Models/ Small Signals/ Quasistatic I V C dt Amp-Sec/Farad V I dt Volt-Sec/Henry 1. Switched
More informationConverter System Modeling via MATLAB/Simulink
Converter System Modeling via MATLAB/Simulink A powerful environment for system modeling and simulation MATLAB: programming and scripting environment Simulink: block diagram modeling environment that runs
More informationSinusoidal Steady-State Analysis
Sinusoidal Steady-State Analysis Almost all electrical systems, whether signal or power, operate with alternating currents and voltages. We have seen that when any circuit is disturbed (switched on or
More informationChapter 9: Controller design
Chapter 9. Controller Design 9.1. Introduction 9.2. Effect of negative feedback on the network transfer functions 9.2.1. Feedback reduces the transfer function from disturbances to the output 9.2.2. Feedback
More informationChapter 3. Steady-State Equivalent Circuit Modeling, Losses, and Efficiency
Chapter 3. Steady-State Equivalent Circuit Modeling, Losses, and Efficiency 3.1. The dc transformer model 3.2. Inclusion of inductor copper loss 3.3. Construction of equivalent circuit model 3.4. How to
More informationProf. Anyes Taffard. Physics 120/220. Voltage Divider Capacitor RC circuits
Prof. Anyes Taffard Physics 120/220 Voltage Divider Capacitor RC circuits Voltage Divider The figure is called a voltage divider. It s one of the most useful and important circuit elements we will encounter.
More information09/29/2009 Reading: Hambley Chapter 5 and Appendix A
EE40 Lec 10 Complex Numbers and Phasors Prof. Nathan Cheung 09/29/2009 Reading: Hambley Chapter 5 and Appendix A Slide 1 OUTLINE Phasors as notation for Sinusoids Arithmetic with Complex Numbers Complex
More informationPhasors: Impedance and Circuit Anlysis. Phasors
Phasors: Impedance and Circuit Anlysis Lecture 6, 0/07/05 OUTLINE Phasor ReCap Capacitor/Inductor Example Arithmetic with Complex Numbers Complex Impedance Circuit Analysis with Complex Impedance Phasor
More informationModule 4. Single-phase AC circuits. Version 2 EE IIT, Kharagpur
Module 4 Single-phase circuits ersion EE T, Kharagpur esson 6 Solution of urrent in Parallel and Seriesparallel ircuits ersion EE T, Kharagpur n the last lesson, the following points were described:. How
More informationR-L-C Circuits and Resonant Circuits
P517/617 Lec4, P1 R-L-C Circuits and Resonant Circuits Consider the following RLC series circuit What's R? Simplest way to solve for is to use voltage divider equation in complex notation. X L X C in 0
More informationLecture 05 Power in AC circuit
CA2627 Building Science Lecture 05 Power in AC circuit Instructor: Jiayu Chen Ph.D. Announcement 1. Makeup Midterm 2. Midterm grade Grade 25 20 15 10 5 0 10 15 20 25 30 35 40 Grade Jiayu Chen, Ph.D. 2
More informationPower Electronics
Prof. Dr. Ing. Joachim Böcker Power Electronics 3.09.06 Last Name: Student Number: First Name: Study Program: Professional Examination Performance Proof Task: (Credits) (0) (0) 3 (0) 4 (0) Total (80) Mark
More informationMathematical Modeling and Dynamic Simulation of a Class of Drive Systems with Permanent Magnet Synchronous Motors
Applied and Computational Mechanics 3 (2009) 331 338 Mathematical Modeling and Dynamic Simulation of a Class of Drive Systems with Permanent Magnet Synchronous Motors M. Mikhov a, a Faculty of Automatics,
More informationExperiment 3: Resonance in LRC Circuits Driven by Alternating Current
Experiment 3: Resonance in LRC Circuits Driven by Alternating Current Introduction In last week s laboratory you examined the LRC circuit when constant voltage was applied to it. During this laboratory
More informationSinusoidal steady-state analysis
Sinusoidal steady-state analysis From our previous efforts with AC circuits, some patterns in the analysis started to appear. 1. In each case, the steady-state voltages or currents created in response
More informationAn improved brake squeal source model in the presence of kinematic and friction nonlinearities
An improved brake squeal source model in the presence of kinematic and friction nonlinearities Osman Taha Sen, Jason T. Dreyer, and Rajendra Singh 3 Department of Mechanical Engineering, Istanbul Technical
More informationInternational Journal of Advance Engineering and Research Development SIMULATION OF FIELD ORIENTED CONTROL OF PERMANENT MAGNET SYNCHRONOUS MOTOR
Scientific Journal of Impact Factor(SJIF): 3.134 e-issn(o): 2348-4470 p-issn(p): 2348-6406 International Journal of Advance Engineering and Research Development Volume 2,Issue 4, April -2015 SIMULATION
More information4. Complex Oscillations
4. Complex Oscillations The most common use of complex numbers in physics is for analyzing oscillations and waves. We will illustrate this with a simple but crucially important model, the damped harmonic
More informationFeedback design for the Buck Converter
Feedback design for the Buck Converter Portland State University Department of Electrical and Computer Engineering Portland, Oregon, USA December 30, 2009 Abstract In this paper we explore two compensation
More informationTSTE25 Power Electronics. Lecture 3 Tomas Jonsson ICS/ISY
TSTE25 Power Electronics Lecture 3 Tomas Jonsson ICS/ISY 2016-11-09 2 Outline Rectifiers Current commutation Rectifiers, cont. Three phase Inrush and short circuit current Exercises 5-5, 5-8, 3-100, 3-101,
More informationWhat happens when things change. Transient current and voltage relationships in a simple resistive circuit.
Module 4 AC Theory What happens when things change. What you'll learn in Module 4. 4.1 Resistors in DC Circuits Transient events in DC circuits. The difference between Ideal and Practical circuits Transient
More informationChapter 1 Fundamental Concepts
Chapter 1 Fundamental Concepts 1 Signals A signal is a pattern of variation of a physical quantity, often as a function of time (but also space, distance, position, etc). These quantities are usually the
More informationEE100Su08 Lecture #11 (July 21 st 2008)
EE100Su08 Lecture #11 (July 21 st 2008) Bureaucratic Stuff Lecture videos should be up by tonight HW #2: Pick up from office hours today, will leave them in lab. REGRADE DEADLINE: Monday, July 28 th 2008,
More informationManufacturing Equipment Control
QUESTION 1 An electric drive spindle has the following parameters: J m = 2 1 3 kg m 2, R a = 8 Ω, K t =.5 N m/a, K v =.5 V/(rad/s), K a = 2, J s = 4 1 2 kg m 2, and K s =.3. Ignore electrical dynamics
More informationNotes on Electric Circuits (Dr. Ramakant Srivastava)
Notes on Electric ircuits (Dr. Ramakant Srivastava) Passive Sign onvention (PS) Passive sign convention deals with the designation of the polarity of the voltage and the direction of the current arrow
More informationIntroduction to Biomedical Engineering
Introduction to Biomedical Engineering Biosignal processing Kung-Bin Sung 6/11/2007 1 Outline Chapter 10: Biosignal processing Characteristics of biosignals Frequency domain representation and analysis
More informationL4970A 10A SWITCHING REGULATOR
L4970A 10A SWITCHING REGULATOR 10A OUTPUT CURRENT.1 TO 40 OUTPUT OLTAGE RANGE 0 TO 90 DUTY CYCLE RANGE INTERNAL FEED-FORWARD LINE REGULA- TION INTERNAL CURRENT LIMITING PRECISE.1 ± 2 ON CHIP REFERENCE
More informationSolutions to Problems in Chapter 4
Solutions to Problems in Chapter 4 Problems with Solutions Problem 4. Fourier Series of the Output Voltage of an Ideal Full-Wave Diode Bridge Rectifier he nonlinear circuit in Figure 4. is a full-wave
More information8 Example 1: The van der Pol oscillator (Strogatz Chapter 7)
8 Example 1: The van der Pol oscillator (Strogatz Chapter 7) So far we have seen some different possibilities of what can happen in two-dimensional systems (local and global attractors and bifurcations)
More informationPhysics 116A Notes Fall 2004
Physics 116A Notes Fall 2004 David E. Pellett Draft v.0.9 Notes Copyright 2004 David E. Pellett unless stated otherwise. References: Text for course: Fundamentals of Electrical Engineering, second edition,
More informationBasics of Network Theory (Part-I)
Basics of Network Theory (Part-I) 1. One coulomb charge is equal to the charge on (a) 6.24 x 10 18 electrons (b) 6.24 x 10 24 electrons (c) 6.24 x 10 18 atoms (d) none of the above 2. The correct relation
More informationRobust sliding mode speed controller for hybrid SVPWM based direct torque control of induction motor
ISSN 1 746-7233, England, UK World Journal of Modelling and Simulation Vol. 3 (2007) No. 3, pp. 180-188 Robust sliding mode speed controller for hybrid SVPWM based direct torque control of induction motor
More informationPHYSICS 110A : CLASSICAL MECHANICS HW 2 SOLUTIONS. Here is a sketch of the potential with A = 1, R = 1, and S = 1. From the plot we can see
PHYSICS 11A : CLASSICAL MECHANICS HW SOLUTIONS (1) Taylor 5. Here is a sketch of the potential with A = 1, R = 1, and S = 1. From the plot we can see 1.5 1 U(r).5.5 1 4 6 8 1 r Figure 1: Plot for problem
More informationEECE 2150 Circuits and Signals Final Exam Fall 2016 Dec 9
EECE 2150 Circuits and Signals Final Exam Fall 2016 Dec 9 Name: Instructions: Write your name and section number on all pages Closed book, closed notes; Computers and cell phones are not allowed You can
More informationChapter 31: RLC Circuits. PHY2049: Chapter 31 1
hapter 31: RL ircuits PHY049: hapter 31 1 L Oscillations onservation of energy Topics Damped oscillations in RL circuits Energy loss A current RMS quantities Forced oscillations Resistance, reactance,
More informationSCHOOL OF MATHEMATICS MATHEMATICS FOR PART I ENGINEERING. Self-paced Course
SCHOOL OF MATHEMATICS MATHEMATICS FOR PART I ENGINEERING Self-paced Course MODULE 26 APPLICATIONS TO ELECTRICAL CIRCUITS Module Topics 1. Complex numbers and alternating currents 2. Complex impedance 3.
More informationSchedule. ECEN 301 Discussion #20 Exam 2 Review 1. Lab Due date. Title Chapters HW Due date. Date Day Class No. 10 Nov Mon 20 Exam Review.
Schedule Date Day lass No. 0 Nov Mon 0 Exam Review Nov Tue Title hapters HW Due date Nov Wed Boolean Algebra 3. 3.3 ab Due date AB 7 Exam EXAM 3 Nov Thu 4 Nov Fri Recitation 5 Nov Sat 6 Nov Sun 7 Nov Mon
More informationElectronics and Communication Exercise 1
Electronics and Communication Exercise 1 1. For matrices of same dimension M, N and scalar c, which one of these properties DOES NOT ALWAYS hold? (A) (M T ) T = M (C) (M + N) T = M T + N T (B) (cm)+ =
More informationA Direct Torque Controlled Induction Motor with Variable Hysteresis Band
UKSim 2009: th International Conference on Computer Modelling and Simulation A Direct Torque Controlled Induction Motor with Variable Hysteresis Band Kanungo Barada Mohanty Electrical Engineering Department,
More informationIntroduction to AC Circuits (Capacitors and Inductors)
Introduction to AC Circuits (Capacitors and Inductors) Amin Electronics and Electrical Communications Engineering Department (EECE) Cairo University elc.n102.eng@gmail.com http://scholar.cu.edu.eg/refky/
More informationLinear and Nonlinear Oscillators (Lecture 2)
Linear and Nonlinear Oscillators (Lecture 2) January 25, 2016 7/441 Lecture outline A simple model of a linear oscillator lies in the foundation of many physical phenomena in accelerator dynamics. A typical
More informationPower system modelling under the phasor approximation
ELEC0047 - Power system dynamics, control and stability Thierry Van Cutsem t.vancutsem@ulg.ac.be www.montefiore.ulg.ac.be/~vct October 2018 1 / 16 Electromagnetic transient vs. phasor-mode simulations
More informationPart 4: Electromagnetism. 4.1: Induction. A. Faraday's Law. The magnetic flux through a loop of wire is
1 Part 4: Electromagnetism 4.1: Induction A. Faraday's Law The magnetic flux through a loop of wire is Φ = BA cos θ B A B = magnetic field penetrating loop [T] A = area of loop [m 2 ] = angle between field
More informationMATH 23 Exam 2 Review Solutions
MATH 23 Exam 2 Review Solutions Problem 1. Use the method of reduction of order to find a second solution of the given differential equation x 2 y (x 0.1875)y = 0, x > 0, y 1 (x) = x 1/4 e 2 x Solution
More informationGATE : , Copyright reserved. Web:www.thegateacademy.com
GATE-2016 Index 1. Question Paper Analysis 2. Question Paper & Answer keys : 080-617 66 222, info@thegateacademy.com Copyright reserved. Web:www.thegateacademy.com ANALYSIS OF GATE 2016 Electrical Engineering
More information6.334 Power Electronics Spring 2007
MIT OpenCourseWare http://ocw.mit.edu 6.334 Power Electronics Spring 2007 For information about citing these materials or our Terms of Use, visit: http://ocw.mit.edu/terms. Chapter 1 Introduction and Analysis
More information8 sin 3 V. For the circuit given, determine the voltage v for all time t. Assume that no energy is stored in the circuit before t = 0.
For the circuit given, determine the voltage v for all time t. Assume that no energy is stored in the circuit before t = 0. Spring 2015, Exam #5, Problem #1 4t Answer: e tut 8 sin 3 V 1 For the circuit
More informationAC Circuits Homework Set
Problem 1. In an oscillating LC circuit in which C=4.0 μf, the maximum potential difference across the capacitor during the oscillations is 1.50 V and the maximum current through the inductor is 50.0 ma.
More informationSinusoidal Steady-State Analysis
Chapter 4 Sinusoidal Steady-State Analysis In this unit, we consider circuits in which the sources are sinusoidal in nature. The review section of this unit covers most of section 9.1 9.9 of the text.
More informationBifurcations and Chaos in a Pulse Width Modulation Controlled Buck Converter
Bifurcations and Chaos in a Pulse Width Modulation Controlled Buck Converter Łukasz Kocewiak, Claus Leth Bak, Stig Munk-Nielsen Institute of Energy Technology, Aalborg University, Pontoppidanstræde 101,
More informationFirst-order transient
EIE209 Basic Electronics First-order transient Contents Inductor and capacitor Simple RC and RL circuits Transient solutions Constitutive relation An electrical element is defined by its relationship between
More informationTHE UNIVERSITY OF WESTERN ONTARIO. Applied Mathematics 375a Instructor: Matt Davison. Final Examination December 14, :00 12:00 a.m.
THE UNIVERSITY OF WESTERN ONTARIO London Ontario Applied Mathematics 375a Instructor: Matt Davison Final Examination December 4, 22 9: 2: a.m. 3 HOURS Name: Stu. #: Notes: ) There are 8 question worth
More informationR. W. Erickson. Department of Electrical, Computer, and Energy Engineering University of Colorado, Boulder
. W. Erickson Department of Electrical, Computer, and Energy Engineering University of Colorado, Boulder Part II" Converter Dynamics and Control! 7.!AC equivalent circuit modeling! 8.!Converter transfer
More informationDynamic circuits: Frequency domain analysis
Electronic Circuits 1 Dynamic circuits: Contents Free oscillation and natural frequency Transfer functions Frequency response Bode plots 1 System behaviour: overview 2 System behaviour : review solution
More informationChapter 9 Objectives
Chapter 9 Engr8 Circuit Analysis Dr Curtis Nelson Chapter 9 Objectives Understand the concept of a phasor; Be able to transform a circuit with a sinusoidal source into the frequency domain using phasor
More informationBasic RL and RC Circuits R-L TRANSIENTS: STORAGE CYCLE. Engineering Collage Electrical Engineering Dep. Dr. Ibrahim Aljubouri
st Class Basic RL and RC Circuits The RL circuit with D.C (steady state) The inductor is short time at Calculate the inductor current for circuits shown below. I L E R A I L E R R 3 R R 3 I L I L R 3 R
More information0 t < 0 1 t 1. u(t) =
A. M. Niknejad University of California, Berkeley EE 100 / 42 Lecture 13 p. 22/33 Step Response A unit step function is described by u(t) = ( 0 t < 0 1 t 1 While the waveform has an artificial jump (difficult
More information2.1 The electric field outside a charged sphere is the same as for a point source, E(r) =
Chapter Exercises. The electric field outside a charged sphere is the same as for a point source, E(r) Q 4πɛ 0 r, where Q is the charge on the inner surface of radius a. The potential drop is the integral
More informationPhase Synchronization
Phase Synchronization Lecture by: Zhibin Guo Notes by: Xiang Fan May 10, 2016 1 Introduction For any mode or fluctuation, we always have where S(x, t) is phase. If a mode amplitude satisfies ϕ k = ϕ k
More informationAspects of Continuous- and Discrete-Time Signals and Systems
Aspects of Continuous- and Discrete-Time Signals and Systems C.S. Ramalingam Department of Electrical Engineering IIT Madras C.S. Ramalingam (EE Dept., IIT Madras) Networks and Systems 1 / 45 Scaling the
More informationTHE MAGNUS METHOD FOR SOLVING OSCILLATORY LIE-TYPE ORDINARY DIFFERENTIAL EQUATIONS
THE MAGNUS METHOD FOR SOLVING OSCILLATORY LIE-TYPE ORDINARY DIFFERENTIAL EQUATIONS MARIANNA KHANAMIRYAN Department of Applied Mathematics and Theoretical Physics, University of Cambridge, Wilberforce Road,
More informationLecture 24. Impedance of AC Circuits.
Lecture 4. Impedance of AC Circuits. Don t forget to complete course evaluations: https://sakai.rutgers.edu/portal/site/sirs Post-test. You are required to attend one of the lectures on Thursday, Dec.
More informationCircuits Advanced Topics by Dr. Colton (Fall 2016)
ircuits Advanced Topics by Dr. olton (Fall 06). Time dependence of general and L problems General and L problems can always be cast into first order ODEs. You can solve these via the particular solution
More informationPart II Converter Dynamics and Control
Part II Converter Dynamics and Control 7. AC equivalent circuit modeling 8. Converter transfer functions 9. Controller design 10. Ac and dc equivalent circuit modeling of the discontinuous conduction mode
More informationLAPLACE TRANSFORMATION AND APPLICATIONS. Laplace transformation It s a transformation method used for solving differential equation.
LAPLACE TRANSFORMATION AND APPLICATIONS Laplace transformation It s a transformation method used for solving differential equation. Advantages The solution of differential equation using LT, progresses
More informationNYQUIST STABILITY FOR HYSTERESIS SWITCHING MODE CONTROLLERS
U.P.B. Sci. Bull., Series C, Vol. 78, Iss. 1, 2016 ISSN 2286-3540 NYQUIST STABILITY FOR HYSTERESIS SWITCHING MODE CONTROLLERS Dan OLARU 1 The stability analysis of the non-linear circuits is a challenging
More informationStudy of Chaos and Dynamics of DC-DC Converters BY SAI RAKSHIT VINNAKOTA ANUROOP KAKKIRALA VIVEK PRAYAKARAO
Study of Chaos and Dynamics of DC-DC Converters BY SAI RAKSHIT VINNAKOTA ANUROOP KAKKIRALA VIVEK PRAYAKARAO What are DC-DC Converters?? A DC-to-DC converter is an electronic circuit which converts a source
More informationMIT Weakly Nonlinear Things: Oscillators.
18.385 MIT Weakly Nonlinear Things: Oscillators. Department of Mathematics Massachusetts Institute of Technology Cambridge, Massachusetts MA 02139 Abstract When nonlinearities are small there are various
More informationOutput high order sliding mode control of unity-power-factor in three-phase AC/DC Boost Converter
Output high order sliding mode control of unity-power-factor in three-phase AC/DC Boost Converter JianXing Liu, Salah Laghrouche, Maxim Wack Laboratoire Systèmes Et Transports (SET) Laboratoire SeT Contents
More information