Low-complexity optimization for large-scale MIMO
|
|
- Arleen Miller
- 5 years ago
- Views:
Transcription
1 Low-complexity optimization for large-scale MIMO Maria Gkizeli Telecommunications Systems Institute Technical University of Crete Chania, Greece This work was supported by the Seventh Framework Program of the European Commission under Grant PIOF-GA TRADENET
2 Signal Model and Problem Statement w data x. w 2 2 select K out of N switch 2 3. H 2 XN y1 y 2 y=hwx+n f=hw f H y w K K N Assumptions: N transmit and M = 2 receive antennas. x C: Transmitted symbol. w C N, w 0 = K: Beamforming vector. H = [ [h 1 h 2 ] H C M N h H = 1,1 h1,2... h1,n ] h2,1 h2,2... h2,n : Channel matrix (M = 2). h H m C1 N : Channel from Tx to mth Rx antenna, m = 1,2. n CN(0,σn 2 I): AWGN. 2 36
3 Signal Model and Problem Statement w data x. w 2 2 select K out of N switch 2 3. H 2 XN y1 y 2 y=hwx+n f=hw f H y w K K N Received vector: y = Hwx +n. Maximum-SNR filter: f = Hw. Filter-output SNR: { f E H Hwx 2} { E f H n 2} = E{ x 2 } σn 2 Hw
4 Signal Model and Problem Statement Objective: max Hw w 0 =K 4 36
5 Signal Model and Problem Statement Objective: where max Hw = max max H :,Iw w 0 =K I S w S = {I {1,2,...,N} : I = K} = { } I 1,I 2,...,I ( N. K) 4 36
6 Signal Model and Problem Statement Objective: where max Hw = max max H :,Iw w 0 =K I S w S = {I {1,2,...,N} : I = K} = For a given I S, w(i) = argmax H :,I w. w { } I 1,I 2,...,I ( N. K) 4 36
7 Signal Model and Problem Statement Objective: where max Hw = max max H :,Iw w 0 =K I S w S = {I {1,2,...,N} : I = K} = For a given I S, w(i) = argmax H :,I w. w Our objective becomes P : I opt = argmax I S { } max H :,Iw w { } I 1,I 2,...,I ( N. K) 4 36
8 Signal Model and Problem Statement Objective: where max Hw = max max H :,Iw w 0 =K I S w S = {I {1,2,...,N} : I = K} = For a given I S, w(i) = argmax H :,I w. w Our objective becomes P : I opt = argmax I S w opt = w(i opt ). { } max H :,Iw w { } I 1,I 2,...,I ( N. K) 4 36
9 Polynomial-Complexity Optimal TAS { } P : I opt = argmax max H :,Iw I S w In general, P examines all ( N K) antenna subset combinations 5 36
10 Polynomial-Complexity Optimal TAS { } P : I opt = argmax max H :,Iw I S w In general, P examines all ( N K) antenna subset combinations complexity O(N K ). 5 36
11 Polynomial-Complexity Optimal TAS { } P : I opt = argmax max H :,Iw I S w In general, P examines all ( N K) antenna subset combinations complexity O(N K ). Our contribution: If w = 1 or w k = 1, k = 1,2,...,K, and M = 2, then we identify with complexity O ( N 4) a subset S S that has size S = O ( N 3) and contains the optimal solution I opt of P. 5 36
12 Polynomial-Complexity Optimal TAS Notes: { } P : I opt = argmax max H :,Iw I S w S = O ( N K) O(N 4 ) S = O ( N 3). 6 36
13 Polynomial-Complexity Optimal TAS Notes: { } P : I opt = argmax max H :,Iw I S w S = O ( N K) O(N 4 ) S = O ( N 3). S is the same for (i) w = 1 or (ii) w k =
14 Polynomial-Complexity Optimal TAS Notes: { } P : I opt = argmax max H :,Iw I S w S = O ( N K) O(N 4 ) S = O ( N 3). S is the same for (i) w = 1 or (ii) w k = 1. If w = 1, then and (i) I opt = argmax I S σ max (H :,I ) = argmax H :,I 2 I S (ii) w opt = argmax w H H H Hw. w =1, w 0 =K 6 36
15 Polynomial-Complexity Optimal TAS Case 1: M = 1. { } P : I opt = argmax max H :,Iw I S w H = h H, H :,I = h H I, and { h I w(i) = h I, w = 1 e j arg(hi), w k =
16 Polynomial-Complexity Optimal TAS Case 1: M = 1. { } P : I opt = argmax max H :,Iw I S w H = h H, H :,I = h H I, and { h I w(i) = h I, w = 1 e j arg(hi), w k = 1. Then, I opt = arg max I S arg max I S h I = argmax I S h I 1 = argmax I S h i 2, w = 1 h i, w k = 1. i I i I 7 36
17 Polynomial-Complexity Optimal TAS P : I opt = arg max I S arg max I S We define function select(u;k) = argmax I S whose cost is O(N). h I = argmax I S h I 1 = argmax I S h i 2, w = 1 h i, w k = 1 i I i I u I = argmax u I 1, u C N, I S 8 36
18 Polynomial-Complexity Optimal TAS P : I opt = arg max I S arg max I S We define function select(u;k) = argmax I S h I = argmax I S h I 1 = argmax I S h i 2, w = 1 h i, w k = 1 i I i I u I = argmax u I 1, u C N, I S whose cost is O(N). For M = 1, I opt = select(h;k) complexity O(N). 8 36
19 Polynomial-Complexity Optimal TAS Case 2: M = 2. H = [h 1 h 2 ] H. { } P : max max H :,Iw I S w 9 36
20 Polynomial-Complexity Optimal TAS Case 2: M = 2. { } P : max max H :,Iw I S w H = [h 1 h 2 ] H. We introduce angles φ [ 0, π 2] and θ ( π,π] and define the unit-norm 2 1 vector c(φ,θ) = [ sin(φ) e jθ cos(φ) ], (φ, θ) Φ = [ 0, π ] ( π,π]
21 Polynomial-Complexity Optimal TAS Case 2: M = 2. { } P : max max H :,Iw I S w H = [h 1 h 2 ] H. We introduce angles φ [ 0, π 2] and θ ( π,π] and define the unit-norm 2 1 vector c(φ,θ) = [ sin(φ) e jθ cos(φ) Cauchy-Schwartz Inequality: ], (φ, θ) Φ = a H c(φ,θ) a c(φ,θ) = a }{{} =1 [ 0, π ] ( π,π]
22 Polynomial-Complexity Optimal TAS Case 2: M = 2. { } P : max max H :,Iw I S w H = [h 1 h 2 ] H. We introduce angles φ [ 0, π 2] and θ ( π,π] and define the unit-norm 2 1 vector c(φ,θ) = [ sin(φ) e jθ cos(φ) Cauchy-Schwartz Inequality: ], (φ, θ) Φ = [ 0, π ] ( π,π]. 2 a H c(φ,θ) a c(φ,θ) = a max }{{} (φ,θ) Φ ah c(φ,θ) = a. =1 9 36
23 Polynomial-Complexity Optimal TAS Case 2: M = 2. { } P : max max H :,Iw I S w H = [h 1 h 2 ] H. We introduce angles φ [ 0, π 2] and θ ( π,π] and define the unit-norm 2 1 vector c(φ,θ) = [ sin(φ) e jθ cos(φ) Cauchy-Schwartz Inequality: ], (φ, θ) Φ = [ 0, π ] ( π,π]. 2 a H c(φ,θ) a c(φ,θ) = a max }{{} (φ,θ) Φ ah c(φ,θ) = a. =1 Then, P becomes max max H :,Iw = max I S w max max I S w (φ,θ) Φ 9 36 w H H H. :,I c(φ,θ)
24 Polynomial-Complexity Optimal TAS P : max max max I S w (φ,θ) Φ w H H H :,Ic(φ,θ) We set u(φ,θ) = H H c(φ,θ)
25 Polynomial-Complexity Optimal TAS P : max max max I S w (φ,θ) Φ w H H H :,Ic(φ,θ) We set u(φ,θ) = H H c(φ,θ). Then, H H :,I c(φ,θ) = u I(φ,θ) 10 36
26 Polynomial-Complexity Optimal TAS P : max max max I S w (φ,θ) Φ w H H H :,Ic(φ,θ) We set u(φ,θ) = H H c(φ,θ). Then, H H :,I c(φ,θ) = u I(φ,θ) and P becomes max max max I S w (φ,θ) Φ w H u I (φ,θ) 10 36
27 Polynomial-Complexity Optimal TAS P : max max max I S w (φ,θ) Φ w H H H :,Ic(φ,θ) We set u(φ,θ) = H H c(φ,θ). Then, H H :,I c(φ,θ) = u I(φ,θ) and P becomes max max max I S w (φ,θ) Φ w H u I (φ,θ) = max max max (φ,θ) Φ I S w w H u I (φ,θ)
28 Polynomial-Complexity Optimal TAS P : max max max I S w (φ,θ) Φ w H H H :,Ic(φ,θ) We set u(φ,θ) = H H c(φ,θ). Then, H H :,I c(φ,θ) = u I(φ,θ) and P becomes max max max I S w (φ,θ) Φ w H u I (φ,θ) = max w H u I (φ,θ). } {{ } O(N) max max (φ,θ) Φ I S w 10 36
29 Polynomial-Complexity Optimal TAS P : max max max I S w (φ,θ) Φ w H H H :,Ic(φ,θ) We set u(φ,θ) = H H c(φ,θ). Then, H H :,I c(φ,θ) = u I(φ,θ) and P becomes max max max I S w (φ,θ) Φ w H u I (φ,θ) = max w H u I (φ,θ). } {{ } O(N) max max (φ,θ) Φ I S w I opt (φ,θ) I(φ, θ) }{{} O(N) = (φ,θ) select(u(φ, θ); K). }{{} O(N) 10 36
30 Polynomial-Complexity Optimal TAS P : For fixed (φ,θ), max max (φ,θ) Φ max I S w w H u I (φ,θ) I(φ,θ) = select(u(φ,θ);k) = select u 1 (φ,θ) u 2 (φ,θ). u N (φ,θ) ;K
31 Polynomial-Complexity Optimal TAS P : For fixed (φ,θ), max max (φ,θ) Φ max I S w w H u I (φ,θ) I(φ,θ) = select(u(φ,θ);k) = select u 1 (φ,θ) u 2 (φ,θ). u N (φ,θ) Recall that, for n = 1,...,N, u n (φ,θ) = H H :,n c(φ,θ) H = 1,n sinφ+h2,n ejθ cosφ. ;K
32 Polynomial-Complexity Optimal TAS 12 36
33 Polynomial-Complexity Optimal TAS L 1,4 L 1,3 π/2 L 2,3 φ π/4 L 2,4 L 1,2 L 3,4 0 π π/2 0 π/2 π θ Intersection of two surfaces: L n,m = {(φ,θ) Φ : un (φ,θ) = u m (φ,θ) }
34 Polynomial-Complexity Optimal TAS π π/2 0 π/2 π 0 π/4 π/2 θ φ L 2,3 L 2,4 L 3, C B L 1,4 L 1,3 L 1,2 A Three-curve intersection Three-surface intersection: u n (φ,θ) = u m (φ,θ) = u l (φ,θ), n m, n l, & m l
35 Input: H C 2 N (channel matrix), K {1,...,N} (desired selection) S { } (set of candidates) Ln,m 0 n,m {1,...,N}, n m for{j1,j2,j3} {1,2,...,N}: j1 j2,j1 j3, j2 j3, d [H:,j1 H:,j3] 1 H:,j2 D 1 d 2 2 d1d2 if D 1 then Lj1,j2 1, Lj1,j3 1, Lj2,j3 1 ψ angle(d1d 2 )±cos 1 D λ angle ([ 1 e jψ] d ) µ ψ +λ c null ejλ H H :,j1 HH :,j2 e jµ H H :,j1 HH :,j3 u Hc I = select(u;k) if multiple entries equal the Kth order element, include all in I if I = K S S {I} elseif I = K +1 else I I {j1,j2,j3} { } S S I {j1,j2}, I {j1,j3}, I {j2,j3} I I {j1,j2,j3} { } S S I {j1}, I {j2}, I {j3} for{n,m}: Ln,m = 0, when a curve does not intersect with any other curve c null ([ H H :,n H H ]) :,m u Hc I = select(u;k) if multiple entries equal the Kth order element, include all in I if I = K else S S {I} I I {n,m} { } S S I {m}, I {n} Output: S
36 Simulation Results BER Random (M=2) Optimal (M=1) Proposed (M=2) Total Number of Antennas N Figure : Bit error rate versus total number of transmit antennas N for M = 2 receive antennas and selection of K = 6 transmit antennas. Unimodular beamforming
37 Simulation Results Number of Antenna Selection Sets Exhaustive search Proposed (bound) Proposed (actual) Total Number of Antennas N Figure : Complexity versus total number of transmit antennas N for M = 2 receive antennas and selection of K = 6 transmit antennas. Unimodular beamforming
38 Summary - We developed an algorithm that has complexity O(N 4 ) and identifies a candidate set of size O(N 3 ) that contains the optimal solution of the following problems. Maximum-SNR TAS for N 2 systems with unimodular beamforming. Maximum-SNR TAS for N 2 systems with unit-norm beamforming. Maximum-SNR RAS for 2 N systems with unit-norm beamforming. I opt = argmax I S w opt = argmax w =1, w 0 =K σ max (H :,I ) = argmax H :,I 2, for H 2 N. I S w H H H Hw, for H 2 N. - For all the above problems, the new candidate set is identical! - The principles of our algorithm may be extended to the M > 2 case
39 Signal Model -Stage I (Multiple-Access Stage) Consider FSK modulation. Transmitted signals at the nth transmission, n = 1,2,...,N: Node A [ ] d A (n) [ ] {0,1}, [ ] 0 1 da (n) x A (n) = or = d A (n) Node B [ ] d B (n) [ ] {0,1}, [ ] 0 1 db (n) x B (n) = or = d B (n) Received vector at the nth transmission, n = 1,2,...,N: y R (n) = h AR x A (n)+h BR x B (n)+w(n)
40 Signal Model - Stage I (Multiple-Access Stage) Concatenate signals from N transmissions. Transmitted signal matrix: x A (1) x B (1) X = [ ] x A (2) x B (2) x A x B =.. x A (N) x B (N) 2N 2 Received vector at the relay: y R (1) y R =. = [ ] [ ] h x A x AR B +w = Xh+w. h BR y R (N)
41 Signal Model - Stage I (Multiple-Access Stage) GLRT-optimal detection: min X,h y R Xh 21 36
42 Signal Model - Stage I (Multiple-Access Stage) GLRT-optimal detection: min X,h y R Xh = P : X = argmin{ y R Xh GLRT } X where h GLRT = argmin y R Xh. h 21 36
43 Signal Model - Stage II (Broadcast Stage) ˆX = (x A,x B ) (d A,d B ) XOR d R FSK x R Received signals at nodes A and B: y A = h RA x R +w A, y B = h RB x R +w B. GLRT-optimal detection at node A: ˆx R = argmin xr {min hra y A h RA x R 2} = Q : arg max x R x T R y A ˆx R ˆd R XOR(,d A ) ˆd B = ˆd R d A 22 36
44 Problem Statement P : X = argmin y R Xh GLRT X Q : ˆx R = argmax x R x T R y A Optimal solution of Q complexity O(NlogN). [Alevizos-Fountzoulas-Karystinos-Bletsas, IEEE T-COM, 2016] In general, optimal solution of P O(2 2N ). Correlation between bit sequences: ρ = x T A x B = d T A d B. x A = x B, iff ρ = N. x A x B, iff 0 ρ N 1. Solve P for each ρ: X 0, X 1,..., X N
45 Case ρ = N Case ρ = N: X = [x A x A ] = x A [1 1]. h GLRT = 1 2N [1 1 ]xt A y R = P N : X N = argmin y R 1 x A N x Ax T A y R = argmax x T A y R x A Therefore, P N is equivalent to Q (noncoherent FSK detection) O(NlogN)
46 Case ρ = 0 Case ρ = 0: x B = x c A = 1 N x A P 0 : X0 = argmax x A [x A x c A ]T y R We have shown that P 0 : b max T z b {±1} N where b = 2d A 1 and z(n) = y R (2n 1) y R (2n), n = 1,...,N. Therefore, P 0 is equivalent to noncoherent PSK detection O(NlogN). [Mackenthun, IEEE T-COM, 1994] 25 36
47 Case ρ = 1,2,...,N 1 Case ρ = 1,2,...,N 1: h GLRT = ( X T X ) 1 X T y R = P ρ : ( ) 1 X ρ = argmax X T 2 X X T y R. x T A x B=ρ 26 36
48 Case ρ = 1,2,...,N 1 Case ρ = 1,2,...,N 1: h GLRT = ( X T X ) 1 X T y R = P ρ : ( ) 1 X ρ = argmax X T 2 X X T y R. x T A x B=ρ Consider c C 2, c = 1. Cauchy-Schwarz Inequality: R{c H a} a H c a c = a. { ( ) 1 } P ρ : max max R c H X T 2 X X T y R. c =1 x T A x B=ρ 26 36
49 Case ρ = 1,2,...,N 1 = P ρ : max c =1 { max d T A d B=ρ n=1 } N d A (n)λ n,1 +d B (n)λ n,2 with ] λ n,1 = R {z(n)c H}[ 1 N+ρ 1, λ n,2 = R {z(n)c H}[ 1 N ρ Recall that N+ρ 1 N ρ z(n) = y R (2n 1) y R (2n), n = 1,2,...,N, ρ indicates the number of equal symbols between d A and d B. ]
50 Case ρ = 1,2,...,N 1 = P ρ : max max c =1 I =ρ max d A (1),...,d A (N) { n I (λ n,1 +λ n,2 ) d A (n) + A (n)λ n,1 +(1 d A (n))λ n,2 n Id where I = { n {1,2,...,N} : d A (n) = d B (n) }. = P ρ : max max c =1 I =ρ n I λ n,1 +λ n,2 + + n I max(λ n,1, λ n,2 )
51 Simulation Results 10 0 Coherent Optimal (N=4) Optimal (N=8) Optimal (N=16) Suboptimal (K=200, N=4) Suboptimal (K=200, N=8) Suboptimal (K=200, N=16) Suboptimal (K=200, N=32) Suboptimal (K=200, N=64) BER at node R SNR (db) Figure : BER at relay node R versus SNR for GLRT-optimal and suboptimal noncoherent PNC with sequence length N = 4,8,16,32, and 64 and optimal coherent PNC
52 Conclusions Large-scale optimization problems and algorithms. MIMO: Large number of antennas antenna selection. Bidirectional relaying: Unknown channels processing of long sequences. Polynomial-complexity algorithms for optimal antenna selection and sequence detection. Collection of linear-complexity problems over continuous variables. Approximate algorithms with linear complexity. Strong relation with large-size linear algebra and combinatorics
53 Computation of the Intersections Three-curve intersection Three-surface intersection: u n (φ,θ) = u m (φ,θ) = u l (φ,θ), where n,m,l {1,...,N} with n m, n l, and m l. H H :,n c(φ,θ) = H H :,m c(φ,θ) H = H :,l c(φ,θ) or, equivalently, [ e jλ H H :,n HH :,m e jµ H H :,n H H :,l ] [ 0 c(φ,θ) = 0 ]
54 Unimodular Beamforming Unimodular beamforming approximation algorithm Consider the relaxed version of P max w H w 1,w 2 Ω K 1 H H :,IH :,I w 2. For fixed w 2, w 1 = e j arg(h I H H I w 2), while, for fixed w 1, w 2 = e j arg(h I H H I w 1). Cyclic maximization, starting from an initial w (0), w (t+1) = e j arg(hh :,I H :,Iw (t) ). Continue until w (t+1) w (t) ǫ or for a predefined number of steps
55 Linear-Complexity Suboptimal TAS π/2 L 2,3 L 1,4 L 1,3 B C A φ π/4 L 2,4 L 1,2 L 3,4 0 -π -π/2 0 π/2 π θ Sample (φ,θ) at P points O(PN)
56 Simulation Results 10 2 BER Random (M=2) Optimal (M=1) [25] (M=2) Optimal (M=2) Suboptimal (M=2, P=15) Suboptimal (M=2, P=81) Total Number of Receive Antennas N Figure : Bit error rate versus total number of receive antennas N for M = 2 transmit antennas and selection of K = 6 receive antennas. Total power constraint
57 Low-Complexity TAS for M > 2 Receive Antennas M > 2 receive antennas: - Define c(φ,θ) = sinφ 1 e jθ 1 cosφ 1 sinφ 2. e jθ M 2 cosφ 1...cosφ M 2 sinφ M 1 e jθ M 1 cosφ 1...cosφ M 2 cosφ M 1. - Generate P samples c(φ p,θ p ), p = 1,2,...,P - Form the N 1 vector u(φ p,θ p ) = H H c(φ p,θ p ) - Call select(u(φ p,θ p );K) (returns with O(N) the indices of the K largest in magnitude elements of u(φ p,θ p )). - Obtain P antenna selection subset candidates. - Overall complexity O(NP)
58 Simulation Results BER Random (M=3) Optimal (M=1) [25] (M=3) Suboptimal (M=3, P=24) Suboptimal (M=3, P=225) Suboptimal (M=3, P=784) Suboptimal (M=3, P=1600) Total Number of Received Antennas N Figure : Bit error rate versus total number of receive antennas N for M = 3 transmit antennas and selection of K = 6 receive antennas. Total power constraint
Capacity Region of the Two-Way Multi-Antenna Relay Channel with Analog Tx-Rx Beamforming
Capacity Region of the Two-Way Multi-Antenna Relay Channel with Analog Tx-Rx Beamforming Authors: Christian Lameiro, Alfredo Nazábal, Fouad Gholam, Javier Vía and Ignacio Santamaría University of Cantabria,
More informationEE 5407 Part II: Spatial Based Wireless Communications
EE 5407 Part II: Spatial Based Wireless Communications Instructor: Prof. Rui Zhang E-mail: rzhang@i2r.a-star.edu.sg Website: http://www.ece.nus.edu.sg/stfpage/elezhang/ Lecture II: Receive Beamforming
More informationOn the Use of Division Algebras for Wireless Communication
On the Use of Division Algebras for Wireless Communication frederique@systems.caltech.edu California Institute of Technology AMS meeting, Davidson, March 3rd 2007 Outline A few wireless coding problems
More informationDigital Band-pass Modulation PROF. MICHAEL TSAI 2011/11/10
Digital Band-pass Modulation PROF. MICHAEL TSAI 211/11/1 Band-pass Signal Representation a t g t General form: 2πf c t + φ t g t = a t cos 2πf c t + φ t Envelope Phase Envelope is always non-negative,
More informationExploiting Partial Channel Knowledge at the Transmitter in MISO and MIMO Wireless
Exploiting Partial Channel Knowledge at the Transmitter in MISO and MIMO Wireless SPAWC 2003 Rome, Italy June 18, 2003 E. Yoon, M. Vu and Arogyaswami Paulraj Stanford University Page 1 Outline Introduction
More informationReflected Simplex Codebooks for Limited Feedback MIMO Beamforming
Reflected Simplex Codebooks for Limited Feedback MIMO Beamforming Daniel J. Ryan 1, Iain B. Collings 2 and Jean-Marc Valin 3 1 Dept. of Electronics & Telecommunications., Norwegian University of Science
More informationDetecting Parametric Signals in Noise Having Exactly Known Pdf/Pmf
Detecting Parametric Signals in Noise Having Exactly Known Pdf/Pmf Reading: Ch. 5 in Kay-II. (Part of) Ch. III.B in Poor. EE 527, Detection and Estimation Theory, # 5c Detecting Parametric Signals in Noise
More informationLimited Feedback in Wireless Communication Systems
Limited Feedback in Wireless Communication Systems - Summary of An Overview of Limited Feedback in Wireless Communication Systems Gwanmo Ku May 14, 17, and 21, 2013 Outline Transmitter Ant. 1 Channel N
More informationJournal Watch IEEE Communications- Sept,2018
Journal Watch IEEE Communications- Sept,2018 Varun Varindani Indian Institute of Science, Bangalore September 22, 2018 1 / 16 Organization Likelihood-Based Automatic Modulation Classification in OFDM With
More informationModulation-Specific Multiuser Transmit. Precoding and User Selection for BPSK Signalling
Modulation-Specific Multiuser Transmit 1 Precoding and User Selection for BPSK Signalling Majid Bavand, Student Member, IEEE, Steven D. Blostein, Senior Member, IEEE arxiv:1603.04812v2 [cs.it] 7 Oct 2016
More informationSingle-User MIMO systems: Introduction, capacity results, and MIMO beamforming
Single-User MIMO systems: Introduction, capacity results, and MIMO beamforming Master Universitario en Ingeniería de Telecomunicación I. Santamaría Universidad de Cantabria Contents Introduction Multiplexing,
More informationCOM Optimization for Communications 8. Semidefinite Programming
COM524500 Optimization for Communications 8. Semidefinite Programming Institute Comm. Eng. & Dept. Elect. Eng., National Tsing Hua University 1 Semidefinite Programming () Inequality form: min c T x s.t.
More informationON DECREASING THE COMPLEXITY OF LATTICE-REDUCTION-AIDED K-BEST MIMO DETECTORS.
17th European Signal Processing Conference (EUSIPCO 009) Glasgow, Scotland, August 4-8, 009 ON DECREASING THE COMPLEXITY OF LATTICE-REDUCTION-AIDED K-BEST MIMO DETECTORS. Sandra Roger, Alberto Gonzalez,
More informationA New SLNR-based Linear Precoding for. Downlink Multi-User Multi-Stream MIMO Systems
A New SLNR-based Linear Precoding for 1 Downlin Multi-User Multi-Stream MIMO Systems arxiv:1008.0730v1 [cs.it] 4 Aug 2010 Peng Cheng, Meixia Tao and Wenjun Zhang Abstract Signal-to-leaage-and-noise ratio
More informationOptimal Receiver for MPSK Signaling with Imperfect Channel Estimation
This full text paper was peer reviewed at the direction of IEEE Communications Society subject matter experts for publication in the WCNC 27 proceedings. Optimal Receiver for PSK Signaling with Imperfect
More informationMulti-Input Multi-Output Systems (MIMO) Channel Model for MIMO MIMO Decoding MIMO Gains Multi-User MIMO Systems
Multi-Input Multi-Output Systems (MIMO) Channel Model for MIMO MIMO Decoding MIMO Gains Multi-User MIMO Systems Multi-Input Multi-Output Systems (MIMO) Channel Model for MIMO MIMO Decoding MIMO Gains Multi-User
More informationELEC E7210: Communication Theory. Lecture 10: MIMO systems
ELEC E7210: Communication Theory Lecture 10: MIMO systems Matrix Definitions, Operations, and Properties (1) NxM matrix a rectangular array of elements a A. an 11 1....... a a 1M. NM B D C E ermitian transpose
More informationA Design of High-Rate Space-Frequency Codes for MIMO-OFDM Systems
A Design of High-Rate Space-Frequency Codes for MIMO-OFDM Systems Wei Zhang, Xiang-Gen Xia and P. C. Ching xxia@ee.udel.edu EE Dept., The Chinese University of Hong Kong ECE Dept., University of Delaware
More informationLinear Programming Detection and Decoding for MIMO Systems
Linear Programming Detection and Decoding for MIMO Systems Tao Cui, Tracey Ho Department of Electrical Engineering California Institute of Technology Pasadena, CA, USA 91125 Email: {taocui, tho}@caltech.edu
More informationAnatoly Khina. Joint work with: Uri Erez, Ayal Hitron, Idan Livni TAU Yuval Kochman HUJI Gregory W. Wornell MIT
Network Modulation: Transmission Technique for MIMO Networks Anatoly Khina Joint work with: Uri Erez, Ayal Hitron, Idan Livni TAU Yuval Kochman HUJI Gregory W. Wornell MIT ACC Workshop, Feder Family Award
More informationSimultaneous SDR Optimality via a Joint Matrix Decomp.
Simultaneous SDR Optimality via a Joint Matrix Decomposition Joint work with: Yuval Kochman, MIT Uri Erez, Tel Aviv Uni. May 26, 2011 Model: Source Multicasting over MIMO Channels z 1 H 1 y 1 Rx1 ŝ 1 s
More informationPhase Precoded Compute-and-Forward with Partial Feedback
Phase Precoded Compute-and-Forward with Partial Feedback Amin Sakzad, Emanuele Viterbo Dept. Elec. & Comp. Sys. Monash University, Australia amin.sakzad,emanuele.viterbo@monash.edu Joseph Boutros, Dept.
More informationSub-modularity and Antenna Selection in MIMO systems
Sub-modularity and Antenna Selection in MIMO systems Rahul Vaze Harish Ganapathy Point-to-Point MIMO Channel 1 1 Tx H Rx N t N r Point-to-Point MIMO Channel 1 1 Tx H Rx N t N r Antenna Selection Transmit
More information3. ESTIMATION OF SIGNALS USING A LEAST SQUARES TECHNIQUE
3. ESTIMATION OF SIGNALS USING A LEAST SQUARES TECHNIQUE 3.0 INTRODUCTION The purpose of this chapter is to introduce estimators shortly. More elaborated courses on System Identification, which are given
More informationL interférence dans les réseaux non filaires
L interférence dans les réseaux non filaires Du contrôle de puissance au codage et alignement Jean-Claude Belfiore Télécom ParisTech 7 mars 2013 Séminaire Comelec Parts Part 1 Part 2 Part 3 Part 4 Part
More informationThe Optimality of Beamforming: A Unified View
The Optimality of Beamforming: A Unified View Sudhir Srinivasa and Syed Ali Jafar Electrical Engineering and Computer Science University of California Irvine, Irvine, CA 92697-2625 Email: sudhirs@uciedu,
More informationHomework 5 Solutions. Problem 1
Homework 5 Solutions Problem 1 (a Closed form Chernoff upper-bound for the uncoded 4-QAM average symbol error rate over Rayleigh flat fading MISO channel with = 4, assuming transmit-mrc The vector channel
More informationDiversity Combining Techniques
Diversity Combining Techniques When the required signal is a combination of several plane waves (multipath), the total signal amplitude may experience deep fades (Rayleigh fading), over time or space.
More informationSecrecy in the 2-User Symmetric Interference Channel with Transmitter Cooperation: Deterministic View
Secrecy in the 2-User Symmetric Interference Channel with Transmitter Cooperation: Deterministic View P. Mohapatra 9 th March 2013 Outline Motivation Problem statement Achievable scheme 1 Weak interference
More informationLattice Reduction Aided Precoding for Multiuser MIMO using Seysen s Algorithm
Lattice Reduction Aided Precoding for Multiuser MIMO using Seysen s Algorithm HongSun An Student Member IEEE he Graduate School of I & Incheon Korea ahs3179@gmail.com Manar Mohaisen Student Member IEEE
More informationUsing Noncoherent Modulation for Training
EE8510 Project Using Noncoherent Modulation for Training Yingqun Yu May 5, 2005 0-0 Noncoherent Channel Model X = ρt M ΦH + W Rayleigh flat block-fading, T: channel coherence interval Marzetta & Hochwald
More informationLayered Orthogonal Lattice Detector for Two Transmit Antenna Communications
Layered Orthogonal Lattice Detector for Two Transmit Antenna Communications arxiv:cs/0508064v1 [cs.it] 12 Aug 2005 Massimiliano Siti Advanced System Technologies STMicroelectronics 20041 Agrate Brianza
More informationOptimal Transmit Strategies in MIMO Ricean Channels with MMSE Receiver
Optimal Transmit Strategies in MIMO Ricean Channels with MMSE Receiver E. A. Jorswieck 1, A. Sezgin 1, H. Boche 1 and E. Costa 2 1 Fraunhofer Institute for Telecommunications, Heinrich-Hertz-Institut 2
More informationConvolutional Codes. Telecommunications Laboratory. Alex Balatsoukas-Stimming. Technical University of Crete. November 6th, 2008
Convolutional Codes Telecommunications Laboratory Alex Balatsoukas-Stimming Technical University of Crete November 6th, 2008 Telecommunications Laboratory (TUC) Convolutional Codes November 6th, 2008 1
More informationMulti-Input Multi-Output Systems (MIMO) Channel Model for MIMO MIMO Decoding MIMO Gains Multi-User MIMO Systems
Multi-Input Multi-Output Systems (MIMO) Channel Model for MIMO MIMO Decoding MIMO Gains Multi-User MIMO Systems Multi-Input Multi-Output Systems (MIMO) Channel Model for MIMO MIMO Decoding MIMO Gains Multi-User
More informationNew Rank-One Matrix Decomposition Techniques and Applications to Signal Processing
New Rank-One Matrix Decomposition Techniques and Applications to Signal Processing Yongwei Huang Hong Kong Baptist University SPOC 2012 Hefei China July 1, 2012 Outline Trust-region subproblems in nonlinear
More informationTitle. Author(s)Tsai, Shang-Ho. Issue Date Doc URL. Type. Note. File Information. Equal Gain Beamforming in Rayleigh Fading Channels
Title Equal Gain Beamforming in Rayleigh Fading Channels Author(s)Tsai, Shang-Ho Proceedings : APSIPA ASC 29 : Asia-Pacific Signal Citationand Conference: 688-691 Issue Date 29-1-4 Doc URL http://hdl.handle.net/2115/39789
More informationConstellation Precoded Beamforming
Constellation Precoded Beamforming Hong Ju Park and Ender Ayanoglu Center for Pervasive Communications and Computing Department of Electrical Engineering and Computer Science University of California,
More informationMode Selection for Multi-Antenna Broadcast Channels
Mode Selection for Multi-Antenna Broadcast Channels Gill November 22, 2011 Gill (University of Delaware) November 22, 2011 1 / 25 Part I Mode Selection for MISO BC with Perfect/Imperfect CSI [1]-[3] Gill
More informationLecture 7 MIMO Communica2ons
Wireless Communications Lecture 7 MIMO Communica2ons Prof. Chun-Hung Liu Dept. of Electrical and Computer Engineering National Chiao Tung University Fall 2014 1 Outline MIMO Communications (Chapter 10
More informationPhysical Layer Network Coding for Two-Way Relaying with QAM
Physical Layer Network Coding for Two-Way Relaying with QAM Vishnu Namboodiri, Kiran Venugopal and B. Sundar Rajan Qualcomm India Private Limited, Hyderabad, India- 500081 Dept. of ECE, Indian Institute
More informationHEURISTIC METHODS FOR DESIGNING UNIMODULAR CODE SEQUENCES WITH PERFORMANCE GUARANTEES
HEURISTIC METHODS FOR DESIGNING UNIMODULAR CODE SEQUENCES WITH PERFORMANCE GUARANTEES Shankarachary Ragi Edwin K. P. Chong Hans D. Mittelmann School of Mathematical and Statistical Sciences Arizona State
More informationWhen does vectored Multiple Access Channels (MAC) optimal power allocation converge to an FDMA solution?
When does vectored Multiple Access Channels MAC optimal power allocation converge to an FDMA solution? Vincent Le Nir, Marc Moonen, Jan Verlinden, Mamoun Guenach Abstract Vectored Multiple Access Channels
More informationTHE concept of wireless systems employing a large number
5016 IEEE TRANSACTIONS ON COMMUNICATIONS, VOL. 61, NO. 12, DECEMBER 2013 Noncoherent Trellis Coded Quantization: A Practical Limited Feedback Technique for Massive MIMO Systems Junil Choi, Zachary Chance,
More informationCooperative Transmission for Wireless Relay Networks Using Limited Feedback
1 Cooperative Transmission for Wireless Relay Networks Using Limited Feedback Javier M. Paredes, Babak H. Khalaj, and Alex B. Gershman arxiv:0904.1369v2 [cs.it] 29 Jul 2009 Abstract To achieve the available
More informationDiversity Performance of a Practical Non-Coherent Detect-and-Forward Receiver
Diversity Performance of a Practical Non-Coherent Detect-and-Forward Receiver Michael R. Souryal and Huiqing You National Institute of Standards and Technology Advanced Network Technologies Division Gaithersburg,
More informationNovel spectrum sensing schemes for Cognitive Radio Networks
Novel spectrum sensing schemes for Cognitive Radio Networks Cantabria University Santander, May, 2015 Supélec, SCEE Rennes, France 1 The Advanced Signal Processing Group http://gtas.unican.es The Advanced
More informationThis examination consists of 11 pages. Please check that you have a complete copy. Time: 2.5 hrs INSTRUCTIONS
THE UNIVERSITY OF BRITISH COLUMBIA Department of Electrical and Computer Engineering EECE 564 Detection and Estimation of Signals in Noise Final Examination 6 December 2006 This examination consists of
More informationCognitive MIMO Radar
Cognitive MIMO Radar Joseph Tabriian Signal Processing Laboratory Department of Electrical and Computer Engineering Ben-Gurion University of the Negev Involved collaborators and Research Assistants: Prof.
More informationThis document is downloaded from DR-NTU, Nanyang Technological University Library, Singapore.
This document is donloaded from DR-NTU, Nanyang Technological University Library, Singapore. Title Amplify-and-forard based to-ay relay ARQ system ith relay combination Author(s) Luo, Sheng; Teh, Kah Chan
More informationSingle-Symbol ML Decodable Distributed STBCs for Partially-Coherent Cooperative Networks
This full text paper was peer reviewed at the direction of IEEE Communications Society subject matter experts for publication in the ICC 2008 proceedings Single-Symbol ML Decodable Distributed STBCs for
More informationCoherentDetectionof OFDM
Telematics Lab IITK p. 1/50 CoherentDetectionof OFDM Indo-UK Advanced Technology Centre Supported by DST-EPSRC K Vasudevan Associate Professor vasu@iitk.ac.in Telematics Lab Department of EE Indian Institute
More informationLinear Processing for the Downlink in Multiuser MIMO Systems with Multiple Data Streams
Linear Processing for the Downlin in Multiuser MIMO Systems with Multiple Data Streams Ali M. Khachan, Adam J. Tenenbaum and Raviraj S. Adve Dept. of Electrical and Computer Engineering, University of
More informationPolynomial-Complexity Computation of the M-phase Vector that Maximizes a Rank-Deficient Quadratic Form
TECHNICAL UNIVERSITY OF CRETE DEPARTENT OF ELECTRONIC AND COPUTER ENGINEERING Polynomial-Complexity Computation of the -phase Vector that aximizes a Rank-Deficient Quadratic Form SUBITTED IN PARTIAL FULFILLENT
More informationReduced Complexity Sphere Decoding for Square QAM via a New Lattice Representation
Reduced Complexity Sphere Decoding for Square QAM via a New Lattice Representation Luay Azzam and Ender Ayanoglu Department of Electrical Engineering and Computer Science University of California, Irvine
More informationLecture 7: Wireless Channels and Diversity Advanced Digital Communications (EQ2410) 1
Wireless : Wireless Advanced Digital Communications (EQ2410) 1 Thursday, Feb. 11, 2016 10:00-12:00, B24 1 Textbook: U. Madhow, Fundamentals of Digital Communications, 2008 1 / 15 Wireless Lecture 1-6 Equalization
More informationarxiv:cs/ v1 [cs.it] 11 Sep 2006
0 High Date-Rate Single-Symbol ML Decodable Distributed STBCs for Cooperative Networks arxiv:cs/0609054v1 [cs.it] 11 Sep 2006 Zhihang Yi and Il-Min Kim Department of Electrical and Computer Engineering
More informationResidual Versus Suppressed-Carrier Coherent Communications
TDA Progress Report -7 November 5, 996 Residual Versus Suppressed-Carrier Coherent Communications M. K. Simon and S. Million Communications and Systems Research Section This article addresses the issue
More informationQAM Constellations for BICM-ID
Efficient Multi-Dimensional Mapping Using 1 QAM Constellations for BICM-ID Hassan M. Navazi and Md. Jahangir Hossain, Member, IEEE arxiv:1701.01167v1 [cs.it] 30 Dec 2016 The University of British Columbia,
More informationBlind Channel Identification in (2 1) Alamouti Coded Systems Based on Maximizing the Eigenvalue Spread of Cumulant Matrices
Blind Channel Identification in (2 1) Alamouti Coded Systems Based on Maximizing the Eigenvalue Spread of Cumulant Matrices Héctor J. Pérez-Iglesias 1, Daniel Iglesia 1, Adriana Dapena 1, and Vicente Zarzoso
More informationChapter 4: Continuous channel and its capacity
meghdadi@ensil.unilim.fr Reference : Elements of Information Theory by Cover and Thomas Continuous random variable Gaussian multivariate random variable AWGN Band limited channel Parallel channels Flat
More informationDecision-Point Signal to Noise Ratio (SNR)
Decision-Point Signal to Noise Ratio (SNR) Receiver Decision ^ SNR E E e y z Matched Filter Bound error signal at input to decision device Performance upper-bound on ISI channels Achieved on memoryless
More informationJoint FEC Encoder and Linear Precoder Design for MIMO Systems with Antenna Correlation
Joint FEC Encoder and Linear Precoder Design for MIMO Systems with Antenna Correlation Chongbin Xu, Peng Wang, Zhonghao Zhang, and Li Ping City University of Hong Kong 1 Outline Background Mutual Information
More informationAchievable Outage Rate Regions for the MISO Interference Channel
Achievable Outage Rate Regions for the MISO Interference Channel Johannes Lindblom, Eleftherios Karipidis and Erik G. Larsson Linköping University Post Print N.B.: When citing this work, cite the original
More informationELG7177: MIMO Comunications. Lecture 3
ELG7177: MIMO Comunications Lecture 3 Dr. Sergey Loyka EECS, University of Ottawa S. Loyka Lecture 3, ELG7177: MIMO Comunications 1 / 29 SIMO: Rx antenna array + beamforming single Tx antenna multiple
More informationAn Introduction to Linear Matrix Inequalities. Raktim Bhattacharya Aerospace Engineering, Texas A&M University
An Introduction to Linear Matrix Inequalities Raktim Bhattacharya Aerospace Engineering, Texas A&M University Linear Matrix Inequalities What are they? Inequalities involving matrix variables Matrix variables
More informationThe Concept of Soft Channel Encoding and its Applications in Wireless Relay Networks
The Concept of Soft Channel Encoding and its Applications in Wireless Relay Networks Gerald Matz Institute of Telecommunications Vienna University of Technology institute of telecommunications Acknowledgements
More informationEvent-triggered stabilization of linear systems under channel blackouts
Event-triggered stabilization of linear systems under channel blackouts Pavankumar Tallapragada, Massimo Franceschetti & Jorge Cortés Allerton Conference, 30 Sept. 2015 Acknowledgements: National Science
More informationGolden Space-Time Block Coded Modulation
Golden Space-Time Block Coded Modulation Laura Luzzi Ghaya Rekaya-Ben Othman Jean-Claude Belfiore and Emanuele Viterbo Télécom ParisTech- École Nationale Supérieure des Télécommunications 46 Rue Barrault
More informationTraining-Symbol Embedded, High-Rate Complex Orthogonal Designs for Relay Networks
Training-Symbol Embedded, High-Rate Complex Orthogonal Designs for Relay Networks J Harshan Dept of ECE, Indian Institute of Science Bangalore 56001, India Email: harshan@eceiiscernetin B Sundar Rajan
More informationPhysical Layer and Coding
Physical Layer and Coding Muriel Médard Professor EECS Overview A variety of physical media: copper, free space, optical fiber Unified way of addressing signals at the input and the output of these media:
More informationRobust Transceiver Design for MISO Interference Channel with Energy Harvesting
Robust Transceiver Design for MISO Interference Channel with Energy Harvesting Ming-Min Zhao # Yunlong Cai #2 Qingjiang Shi 3 Benoit Champagne &4 and Min-Jian Zhao #5 # College of Information Science and
More informationAugmented Lattice Reduction for MIMO decoding
Augmented Lattice Reduction for MIMO decoding LAURA LUZZI joint work with G. Rekaya-Ben Othman and J.-C. Belfiore at Télécom-ParisTech NANYANG TECHNOLOGICAL UNIVERSITY SEPTEMBER 15, 2010 Laura Luzzi Augmented
More informationAlgebraic Methods for Wireless Coding
Algebraic Methods for Wireless Coding Frédérique Oggier frederique@systems.caltech.edu California Institute of Technology UC Davis, Mathematics Department, January 31st 2007 Outline The Rayleigh fading
More informationAdvanced Topics in Digital Communications Spezielle Methoden der digitalen Datenübertragung
Advanced Topics in Digital Communications Spezielle Methoden der digitalen Datenübertragung Dr.-Ing. Carsten Bockelmann Institute for Telecommunications and High-Frequency Techniques Department of Communications
More informationDifferential Full Diversity Spatial Modulation using Amplitude Phase Shift Keying
RADIOENGINEERING, VOL 7, NO 1, APRIL 018 151 Differential ull Diversity Spatial Modulation using Amplitude Phase Shift Keying Kavishaur DWARIKA 1, Hongjun XU 1, 1 School of Engineering, University of KwaZulu-Natal,
More informationApplications of Lattices in Telecommunications
Applications of Lattices in Telecommunications Dept of Electrical and Computer Systems Engineering Monash University amin.sakzad@monash.edu Oct. 2013 1 Sphere Decoder Algorithm Rotated Signal Constellations
More informationSoft-Decision-and-Forward Protocol for Cooperative Communication Networks with Multiple Antennas
Soft-Decision-and-Forward Protocol for Cooperative Communication Networks with Multiple Antenn Jae-Dong Yang, Kyoung-Young Song Department of EECS, INMC Seoul National University Email: {yjdong, sky6174}@ccl.snu.ac.kr
More informationIncremental Coding over MIMO Channels
Model Rateless SISO MIMO Applications Summary Incremental Coding over MIMO Channels Anatoly Khina, Tel Aviv University Joint work with: Yuval Kochman, MIT Uri Erez, Tel Aviv University Gregory W. Wornell,
More informationAchievability of Nonlinear Degrees of Freedom in Correlatively Changing Fading Channels
Achievability of Nonlinear Degrees of Freedom in Correlatively Changing Fading Channels Mina Karzand Massachusetts Institute of Technology Cambridge, USA Email: mkarzand@mitedu Lizhong Zheng Massachusetts
More informationMassive MIMO with 1-bit ADC
SUBMITTED TO THE IEEE TRANSACTIONS ON COMMUNICATIONS 1 Massive MIMO with 1-bit ADC Chiara Risi, Daniel Persson, and Erik G. Larsson arxiv:144.7736v1 [cs.it] 3 Apr 14 Abstract We investigate massive multiple-input-multipleoutput
More informationCodes on Graphs. Telecommunications Laboratory. Alex Balatsoukas-Stimming. Technical University of Crete. November 27th, 2008
Codes on Graphs Telecommunications Laboratory Alex Balatsoukas-Stimming Technical University of Crete November 27th, 2008 Telecommunications Laboratory (TUC) Codes on Graphs November 27th, 2008 1 / 31
More informationController Coefficient Truncation Using Lyapunov Performance Certificate
Controller Coefficient Truncation Using Lyapunov Performance Certificate Joëlle Skaf Stephen Boyd Information Systems Laboratory Electrical Engineering Department Stanford University European Control Conference,
More informationImproved Multiple Feedback Successive Interference Cancellation Algorithm for Near-Optimal MIMO Detection
Improved Multiple Feedback Successive Interference Cancellation Algorithm for Near-Optimal MIMO Detection Manish Mandloi, Mohammed Azahar Hussain and Vimal Bhatia Discipline of Electrical Engineering,
More informationMulti-Branch MMSE Decision Feedback Detection Algorithms. with Error Propagation Mitigation for MIMO Systems
Multi-Branch MMSE Decision Feedback Detection Algorithms with Error Propagation Mitigation for MIMO Systems Rodrigo C. de Lamare Communications Research Group, University of York, UK in collaboration with
More informationρ = sin(2π ft) 2π ft To find the minimum value of the correlation, we set the derivative of ρ with respect to f equal to zero.
Problem 5.1 : The correlation of the two signals in binary FSK is: ρ = sin(π ft) π ft To find the minimum value of the correlation, we set the derivative of ρ with respect to f equal to zero. Thus: ϑρ
More informationTruncation for Low Complexity MIMO Signal Detection
1 Truncation for Low Complexity MIMO Signal Detection Wen Jiang and Xingxing Yu School of Mathematics Georgia Institute of Technology, Atlanta, Georgia, 3033 Email: wjiang@math.gatech.edu, yu@math.gatech.edu
More informationDigital Modulation 1
Digital Modulation 1 Lecture Notes Ingmar Land and Bernard H. Fleury Navigation and Communications () Department of Electronic Systems Aalborg University, DK Version: February 5, 27 i Contents I Basic
More informationThis examination consists of 10 pages. Please check that you have a complete copy. Time: 2.5 hrs INSTRUCTIONS
THE UNIVERSITY OF BRITISH COLUMBIA Department of Electrical and Computer Engineering EECE 564 Detection and Estimation of Signals in Noise Final Examination 08 December 2009 This examination consists of
More informationOptimum Relay Position for Differential Amplify-and-Forward Cooperative Communications
Optimum Relay Position for Differential Amplify-and-Forard Cooperative Communications Kazunori Hayashi #1, Kengo Shirai #, Thanongsak Himsoon 1, W Pam Siriongpairat, Ahmed K Sadek 3,KJRayLiu 4, and Hideaki
More informationThe Zariski Spectrum of a ring
Thierry Coquand September 2010 Use of prime ideals Let R be a ring. We say that a 0,..., a n is unimodular iff a 0,..., a n = 1 We say that Σa i X i is primitive iff a 0,..., a n is unimodular Theorem:
More informationConstrained Detection for Multiple-Input Multiple-Output Channels
Constrained Detection for Multiple-Input Multiple-Output Channels Tao Cui, Chintha Tellambura and Yue Wu Department of Electrical and Computer Engineering University of Alberta Edmonton, AB, Canada T6G
More informationSPECTRUM SHARING IN WIRELESS NETWORKS: A QOS-AWARE SECONDARY MULTICAST APPROACH WITH WORST USER PERFORMANCE OPTIMIZATION
SPECTRUM SHARING IN WIRELESS NETWORKS: A QOS-AWARE SECONDARY MULTICAST APPROACH WITH WORST USER PERFORMANCE OPTIMIZATION Khoa T. Phan, Sergiy A. Vorobyov, Nicholas D. Sidiropoulos, and Chintha Tellambura
More informationLecture 3: Review of Linear Algebra
ECE 83 Fall 2 Statistical Signal Processing instructor: R Nowak Lecture 3: Review of Linear Algebra Very often in this course we will represent signals as vectors and operators (eg, filters, transforms,
More informationTransmitter-Receiver Cooperative Sensing in MIMO Cognitive Network with Limited Feedback
IEEE INFOCOM Workshop On Cognitive & Cooperative Networks Transmitter-Receiver Cooperative Sensing in MIMO Cognitive Network with Limited Feedback Chao Wang, Zhaoyang Zhang, Xiaoming Chen, Yuen Chau. Dept.of
More informationSummary: SER formulation. Binary antipodal constellation. Generic binary constellation. Constellation gain. 2D constellations
TUTORIAL ON DIGITAL MODULATIONS Part 8a: Error probability A [2011-01-07] 07] Roberto Garello, Politecnico di Torino Free download (for personal use only) at: www.tlc.polito.it/garello 1 Part 8a: Error
More informationMultiuser Capacity in Block Fading Channel
Multiuser Capacity in Block Fading Channel April 2003 1 Introduction and Model We use a block-fading model, with coherence interval T where M independent users simultaneously transmit to a single receiver
More informationLecture 3: Review of Linear Algebra
ECE 83 Fall 2 Statistical Signal Processing instructor: R Nowak, scribe: R Nowak Lecture 3: Review of Linear Algebra Very often in this course we will represent signals as vectors and operators (eg, filters,
More informationNon-coherent Multi-layer Constellations for Unequal Error Protection
Non-coherent Multi-layer Constellations for Unequal Error Protection Kareem M. Attiah, Karim Seddik, Ramy H. Gohary and Halim Yanikomeroglu Department of Electrical Engineering, Alexandria University,
More informationModulation & Coding for the Gaussian Channel
Modulation & Coding for the Gaussian Channel Trivandrum School on Communication, Coding & Networking January 27 30, 2017 Lakshmi Prasad Natarajan Dept. of Electrical Engineering Indian Institute of Technology
More information